1
Semiconductor
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
Copyright
Harris Corporation 1998
HIP5600
Thermally Protected High Voltage Linear
Regulator
The HIP5600 is an adjustable 3-terminal positive linear
voltage regulator capable of operating up to either 400V
DC
or 280V
RMS
. The output voltage is adjustable from 1.2V
DC
to within 50V of the peak input voltage with two external
resistors. This high voltage linear regulator is capable of
sourcing 1mA to 30mA with proper heat sinking. The
HIP5600 can also provide 40mA peak (typical) for short
periods of time.
Protection is provided by the on chip thermal shutdown and
output current limiting circuitry. The HIP5600 has a unique
advantage over other high voltage linear regulators due to its
ability to withstand input to output voltages as high as
400V(peak), a condition that could exist under output short
circuit conditions.
Common linear regulator configurations can be implemented
as well as AC/DC conversion and start-up circuits for switch
mode power supplies.
The HIP5600 requires a minimum output capacitor of 10
F
for stability of the output and may require a 0.02
F input
decoupling capacitor depending on the source impedance. It
also requires a minimum load current of 1mA to maintain
output voltage regulation.
All protection circuitry remains fully functional even if the
adjustment terminal is disconnected. However, if this
happens the output voltage will approach the input voltage.
Features
Operates from 50V
DC
to 400V
DC
Operates from 50V
RMS
to 280V
RMS
Line
UL Recognized
Variable DC Output Voltage 1.2V
DC
to V
IN
- 50V
Internal Thermal Shutdown Protection
Internal Over Current Protection
Up to 40mA Peak Output Current
Surge Rated to
650V; Meets IEEE/ANSI C62.41.1980
with Additional MOV
CAUTION: This product does not provide isolation from AC
line.
Applications
Switch Mode Power Supply Start-Up
Electronically Commutated Motor Housekeeping Supply
Power Supply for Simple Industrial/Commercial/Consumer
Equipment Controls
Off-Line (Buck) Switch Mode Power Supply
Pinouts
HIP5600 (TO-220)
TOP VIEW
HIP5600 (MO-169)
TOP VIEW
Ordering Information
PART
NUMBER
TEMP. RANGE
PACKAGE
HIP5600IS
-40
o
C to +100
o
C
3 Lead Plastic SIP
HIP5600IS2
-40
o
C to +100
o
C
3 Lead Gullwing Plastic
SIP
ADJ
V
OUT
V
IN
TAB ELECTRICALLY
CONNECTED
TO V
OUT
V
OUT
HIP5600
ADJ
V
OUT
V
IN
September 1998
File Number
3270.7
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PART WITHDRA
WN
PROCESS OBSOLETE
NO NEW DESIGNS
2
Functional Block Diagram
Schematic Diagram
FIGURE 1.
-
+
+
-
SHORT-CIRCUIT
PROTECTION
-
+
VOLTAGE
V
OUT
RF1
ADJ
RF2
PASS
TRANSISTOR
REFERENCE
FEEDBACK
OR CONTROL
AMPLIFIER
BIAS
NETWORK
THERMAL
SHUTDOWN
RECTIFIER FOR
AC OPERATION
+
-
V
IN
C1
HIP5600
C2
ADJ
D1
D2
R1
D4
Q1
R2
D3
R3
Q4
D5
R4
R5
R7
Q3
R6
Q5
Q6
D6
Q7
Q8
Q9
D7
D8
Q10
R10
R11
Q2
Q11
R12
R13
D9
Q12
Q14
Q13
R15
C1
V
IN
R14
R8
R9
V
OUT
HIP5600
3
Absolute Maximum Ratings
Thermal Information
(Typical)
Input to Output Voltage, Continuous. . . . . . . . . . . . . +480V to -550V
Input to Output Voltage, Peak (Non Repetitive, 2ms)
. . . . . . . .
650V
Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +150
o
C
ADJ to Output, Voltage to ADJ
. . . . . . . . . . . . . . . . . . . . . . . . . . . . .
5V
Storage Temperature Range . . . . . . . . . . . . . . . . . -65
o
C to +150
o
C
Lead Temperature (Soldering 10s) . . . . . . . . . . . . . . . . . . . . +265
o
C
Thermal Resistance
JA
JC
Plastic SIP Package . . . . . . . . . . . . . .
60
o
C/W
4
o
C/W
CAUTION: Stresses above those listed in "Absolute Maximum Ratings" may cause permanent damage to the device. This is a stress only rating and operation
of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied.
Operating Conditions
Operating Voltage Range . . . . . . . . . . . . . . 80V
RMS
to 280V
RMS
or
50V
DC
to 400V
DC
Operating Temperature Range . . . . . . . . . . . . . . . .-40
o
C to +100
o
C
Electrical Specifications
Conditions V
IN
= 400VDC, I
L
= 1mA, C
L
= 10
F, V
ADJ
= 3.79V, V
OUT
= 5V (Unless Otherwise Specified) Tem-
perature = Case Temperature.
PARAMETER
CONDITION
TEMP
MIN
TYP
MAX
UNITS
INPUT
Input Voltage
DC
Full
50
-
400
V
Max Peak Input Voltage
Non-Repetitive (2ms)
Full
-
-
650
V
Input Frequency (Note 1)
Full
DC
-
1000
Hz
Bias Current (I
BIAS
Note 2)
Full
0.4
0.5
0.6
mA
REFERENCE
I
ADJ
+25
o
C
50
65
80
A
I
ADJ
T
C
(Note 1)
I
L
= 1mA
Full
-
+0.15
-
A/
o
C
I
ADJ LOAD REG
(Note 1)
I
L
= 1mA to 10mA
+25
o
C
-
-215
-
nA/mA
V
REF
(Note 3)
+25
o
C
1.07
1.18
1.30
V
V
REF
T
C
(Note 1)
I
L
= 1mA
Full
-
-460
-
V/
o
C
Line Regulation
V
REF LINE REG
50VDC to 400VDC
+25
o
C
-
9
14.5
V/V
Full
-
9
29
V/V
Load Regulation
V
REF LOAD REG
I
OUT
= 1mA to 10mA
+25
o
C
-
3
5
mV/mA
Full
-
3
6
mV/mA
PROTECTION CIRCUITS
Output Short Circuit Current Limit
V
IN
= 50V
+25
o
C
35
-
45
mA
Thermal Shutdown T
TS
(IC surface, not case temperature. Note 1)
V
IN
= 400V
-
127
134
142
o
C
Thermal Shutdown Hysteresis (Note 1)
V
IN
= 400V
-
-
34
-
o
C
NOTES:
1. Characterized not tested
2. Bias current
input current with output pin floating.
3. V
REF
= V
OUT
- V
ADJ
HIP5600
4
Application Information
Introduction
In many electronic systems the components operate at 3V to
15V but the system obtains power from a high voltage
source (AC or DC). When the current requirements are
small, less than 10mA, a linear regulator may be the best
supply provided that it is easy to design in, reliable, low cost
and compact. The HIP5600 is similar to other 3 terminal reg-
ulators but operates from much higher voltages. It protects
its load from surges
+
250V above its 400V operating input
voltage and has short circuit current limiting and thermal
shutdown self protection features.
Output Voltage
The HIP5600 provides a temperature independent 1.18V
reference, V
REF
, between the output and the adjustment
terminal (V
REF
= V
OUT
- V
ADJ
). This constant reference
voltage is impressed across RF1 (see Figure 2) and results
in a constant current (I
1
) that flows through RF2 to ground.
The voltage across RF2 is the product of its resistance and
the sum of I
1
and I
ADJ.
The output voltage is given in Equa-
tions 1(A, B).
(EQ. 1A)
(EQ. 1B)
Equations 2(A,B,C) are provided to determine the worst
case output voltage in relation to; manufacturing tolerances
(
V
REF
and
I
REF
),% tolerance in external resistors
(
RF1/RF1,
RF2/RF2), load regulation (
VREF LOAD REG
,
IADJ LOAD REG
), line regulation (V
REF LINE REG
) and the
effects of temperature (V
REF
TC, I
REF
TC), which includes
self heating (
SA
).
FIGURE 2.
Example:
Given:
V
IN
= 200V
DC
, V
OUT
= 15V, I
OUT
=
2mA to 12mA
,
SA
= 10
o
C/W, RF1 = 1.1k
5% low, RF2 =
12k
5% high,
I
OUT
equals 10mA and
Temp equals
+60
o
C (ambient temperature +25
o
C to +85
o
C). The worst
case
V
OUT
for the given conditions is -1.13V. The shift in
V
OUT
is attributed to the following: -1.55V manufacturing tol-
erances, +1.33V external resistors, -0.62V load regulation
and -0.29V temperature effects.
Regulator With Zener
FIGURE 3.
The output voltage can be set by using a zener diode (Figure
3) instead of the resistor divider shown in Figure 2. The
zener diode improves the ripple rejection ratio and reduces
the value of the worst case output voltage, as illustrated in
the example to follow. The bias current of the zener diode is
set by the value of RF1 and I
ADJ
.
The regulator / zener diode becomes an attractive solution if
ripple rejection or the worst case tolerance of the output volt-
age is critical (i.e. one zener diode cost less than one 10
F
capacitor (C3) and one 1/4W resistor RF2). Minimum power
dissipation is possible by reducing I
1
current, with little effect
on the output voltage regulation. The output voltage is given
in Equation 3.
Equations 4(A,B,C) are provided to determine the worst
case output voltage in relation to; manufacturing tolerances
V
OUT
V
REF
(
)
RF1
RF2
+
RF1
------------------------------
I
ADJ
RF2
(
)
+
=
V
OUT
1.18
(
)
RF1
RF2
+
RF1
------------------------------
65
A RF2
(
)
+
=
(EQ. 2A)
Where;
+V
REF
RF2
RF1
----------
RF2
RF2
--------------
RF1
RF1
--------------
V
REF
T
V
REF
V
REFLOADREG
I
OUT
(
)
V
REF
T C
T e m p
(
)
+
+
ITADJ
I
ADJ
I
ADJLOADREG
I
OUT
(
)
I
ADJ
+
T C
T e m p
(
)
+
(EQ. 2B)
(EQ. 2C)
Error Budget
Note:
RFx
RFx
---------------
= % tolerance of resistor x
V
OUT
VTREF
R F 1
R F 2
+
R F 1
--------------------------
ITADJRF2
I
ADJ
R F 2
R F 2
R F 2
-------------
+
+
=
+ V
REF
T C
SA
(
)
I
OUT
V
IN
(
)
V
+
REFLINEREG
+ I
ADJ
T C
SA
(
)
I
OUT
V
IN
(
)
V
OUT(NOMINAL)
RF1
RF2
3.3V
3.6k
5.6k
4.9V
2.7k
7.5k
12.0V
1.8k
15k
14.8V
1.1k
12k
AC/DC
ADJ
V
OUT
V
IN
HIP5600
V
OUT
I
1
RF1
V
REF
I
ADJ
AC/DC
RF2
AC/DC
ADJ
V
OUT
V
IN
HIP5600
V
OUT
I
1
RF1
V
REF
I
ADJ
V
Z
AC/DC
V
OUT
= 1.18 + V
Z
V
OUT
V
Z
3.7V
2.5V
5.1V
3.9V
10.3V
9.1V
12.2V
11V
16.2V
15V
RF1 = 10k
HIP5600
5
of HIP5600 and the zener diode (
V
REF
and
V
z
), load reg-
ulation of the HIP5600 (V
REF LOAD REG
), and the effects of
temperature on the HIP5600 and the zener diode (V
REF
TC,
V
Z
TC).
Example:
Given:
V
IN
= 200V, V
OUT
= 14.18V (V
REF
=
1.18V, V
Z
= 13V),
V
Z
= 5%, V
Z
TC
= +
0.079%
/
C
(
assumes
1N5243BPH)
,
I
OUT
equal 10mA and
Temp equal +60
o
C.
The worst case
V
OUT
is 0.4956V. The shift in V
OUT
is
attributed to the following: -0.2 (HIP5600) and 0.69 (zener
diode).
The regulator/zener diode configuration gives a 3.5%
(0.49/14.18) worst case output voltage error where, for the
same conditions, the regulator/resistor configuration results
in an 7.5% (1.129/15) worst case output voltage error.
External Capacitors
A minimum10
F output capacitor (C2) is required for stability
of the output stage. Any increase of the load capacitance
greater than 10
F will merely improve the loop stability and
output impedance.
A 0.02
F input decoupling capacitor (C1) between V
IN
and
ground may be required if the power source impedance is
not sufficiently low for the 1MHz - 10MHz band. Without this
capacitor, the HIP5600 can oscillate at 2.5MHz when driven
by a power source with a high impedance for the 1MHz -
10MHz band.
An optional bypass capacitor (C3) from V
ADJ
to ground
improves the ripple rejection by preventing the ripple at the
Adjust pin from being amplified. Bypass capacitors larger
than 10
F do not appreciably improve the ripple rejection of
the part (see Figure 20 through Figure 25).
Load Regulation
For improved load regulation, resistor RF1 (connected
between the adjustment terminal and V
OUT
) should be tied
directly to the output of the regulator (Figure 4A) rather than
near the load Figure 4B. This eliminates line drops (R
S
) from
appearing effectively in series with RF1 and degrading regu-
lation. For example, a 15V regulator with a 0.05
resistance
between the regulator and the load will have a load regula-
tion due to line resistance of 0.05
x
I
L
. If RF1 is con-
nected near the load the effective load regulation will be 11.9
times worse (1+R2/R1, where R2 = 12k, R1 = 1.1k).
FIGURE 4.
Protection Diodes
The HIP5600, unlike other voltage regulators, is internally
protected by input diodes in the event the input becomes
shorted to ground. Therefore, no external protection diode is
required between the input pin and the output pin to protect
against the output capacitor (C2) discharging through the
input to ground.
If the output is shorted in the absence of D1 (Figure 5), the
bypass capacitor voltage (C3) could exceed the absolute
maximum voltage rating of
5V between V
OUT
and V
IN
.
Note; No protection diode (D1) is needed for output voltages
less than 6V or if C3 is not used.
FIGURE 5. REGULATOR WITH PROTECTION DIODE
Selecting the Right Heat Sink
Linear power supplies can dissipate a lot of power. This
power or heat must be safely dissipated to permit continuous
operation. This section will discuss thermal resistance and
show how to calculate heat sink requirements.
Electronic heat sinks are generally rated by their thermal
resistance. Thermal resistance is defined as the temperature
rise per unit of heat transfer or power dissipated, and is
expressed in units of degrees centigrade per watt. For a par-
ticular application determine the thermal resistance (
SA
)
which the heat sink must have in order to maintain a junction
temperature below the thermal shut down limit (T
TS
).
V
OUT
V
REF
V
Z
+
=
(EQ. 3)
V
OUT
VTREF
VT
Z
+
=
(EQ. 4A)
VTREF
V
REF
V
REFLOADREG
I
OUT
(
)
V
REF
T C
T e m p
(
)
+
+
(EQ. 4B)
VTZ
V
Z
t o l e r a n c e V
Z
( )
V
Z
T C
T e m p
(
)
+
(EQ. 4C)
Error Budget
+ V
REF
T C
SA
(
)
I
OUT
V
IN
(
)
V
+
REFLINEREG
AC/DC
AC/DC
I
ADJ
R
S
(A)
(B)
V
REF
V
OUT
ADJ
V
OUT
V
IN
RF1
RF2
HIP5600
I
1
AC/DC
I
ADJ
R
S
V
REF
V
OUT
ADJ
V
OUT
V
IN
RF1
RF2
HIP5600
I
1
AC/DC
V
IN
ADJ
V
OUT
V
IN
+ V
OUT
RF1
RF2
C1
0.02
F
C2
C3
10
F
D1
D1 PROTECTS AGAINST C3
DISCHARGING WHEN THE
OUTPUT IS SHORTED.
HIP5600
10
F
HIP5600
6
A thermal network that describes the heat flow from the inte-
grated circuit to the ambient air is shown in Figure 6. The
basic relation for thermal resistance from the IC surface, his-
torically called "junction", to ambient (
JA
) is given in Equa-
tion 5. The thermal resistance of the heat sink (
SA
) to
maintain a desired junction temperature is calculated using
Equation 6.
FIGURE 6.
Where:
JA
= (Junction to Ambient Thermal Resistance) The sum of
the thermal resistances of the heat flow path.
JA
=
JC
+
CS
+
SA
T
J
=
(Junction Temperature) The desired maximum junc-
tion temperature of the part. T
J
= T
TS
T
TS
=
(Thermal Shutdown Temperature) The maximum
junction temperature that is set by the thermal pro-
tection circuitry of the HIP5600
(min = +127
o
C, typ = +134
o
C and max = +142
o
C).
JC
= (Junction to Case Thermal Resistance) Describes the
thermal resistance from the IC surface to its case.
JC
=
4.8
o
C/W
CS
= (Case to Mounting Surface Thermal Resistance) The
resistance of the mounting interface between the
transistor case and the heat sink.
For example, mica washer.
SA
= (Mounting Surface to Ambient Thermal Resistance)
The resistance of the heat sink to the ambient air.
Varies with air flow.
T
A
= Ambient Temperature
P = The power dissipated by the HIP5600 in watts.
P = (V
IN
- V
OUT
)(I
OUT
)
Worst case
SA
is calculated using the minimum T
TS
of
+127
o
C in Equation 6.
Example,
Given: V
IN
= 400V
DC
V
OUT
= 15V
I
LOAD
= 15mA
JC
= 4.8
o
C/W
T
TS
= +127
C
I
ADJ
= 80
A
T
A
= +50
o
C
RF1 = 1.1k
V
REF
= 1.18V
P = 6.2W = (V
IN
- V
OUT
)(I
IN
)
Find:
Proper heat sink to keep the junction temperature
of the HIP5600 from exceeding T
TS
(+127
o
C).
Solution:
Use Equation 6,
The selection of a heat sink with
SA
less than +7.62
o
C/W
would ensure that the junction temperature would not
exceed the thermal shut down temperature (T
TS
) of +127
o
C.
A Thermalloy P/N7023 at 6.2W power dissipation would
meet this requirement with a
SA
of +5.7
o
C/W.
Operation Without A Heatsink
The package has a
JA
of +60
o
C/W. This allows 0.7W
power dissipation at +85
o
C in still air. Mounting the HIP5600
to a printed circuit board (see Figure 39 through Figure 41)
decreases the thermal impedance sufficiently to allow about
1.6W of power dissipation at +85
o
C in still air.
Thermal Transient Operation
For applications such as start-up, the HIP5600 in the TO-220
package can operate at several watts -without a heat sink-
for a period of time before going into thermal shutdown.
FIGURE 7. THERMAL CAPACITANCE MODEL OF HIP5600
Figure 7 shows the thermal capacitances of the TO-220
package, the integrated circuit and the heat sink, if used.
When power is initially applied, the mass of the package
absorbs heat which limits the rate of temperature rise of the
PD
JC
T
A
= AMBIENT AIR
T
S
= HEAT SINK
T
J
= JUNCTION
SA
HEAT SINK
CS
T
C
= CASE
SA
+
CS
SA
T
TS
T
A
P
----------------------------
JC
=
JA
JC
CS
SA
+
+
=
(EQ. 6)
Where:
JA
T
J
T
A
P
----------------------
=
(EQ. 5)
C
W
--------
T
J
T
TS
=
and
I
IN
I
ADJ
V
REF
RF1
-------------------
I
LOAD
+
+
SA
T
TS
T
A
P
----------------------------
JC
=
SA
127
C 50
C
6.2
-------------------------------------------
4.8
C
7.62
C
W
--------
=
=
(EQ. 7)
(EQ. 8)
P
D
= I
IN
(V
IN
- V
OUT
)
0.6
JC
T
A
= AMBIENT AIR
T
S
= HEAT SINK
T
J
= JUNCTION
SA
0.4
JC
DIE/PACKAGE INTERFACE
0.5C
P
CS + 0.5C
P
OR CASE
C
D
HIP5600
7
junction. With no heat sink C
S
equals zero and
SA
equals the
difference between
JA
and
JC
. The following equations pre-
dict the transient junction temperature and the time to thermal
shutdown for ambient temperatures up to +85
o
C and power
levels up to 8W. The output current limit temperature coeffi-
cient (Figure 39) precludes continuous operation above 8W.
For the TO-220, C
P
is 0.9Ws to 1.1Ws per degree compared
to about 2.6mWs per degree for the integrated circuit and C
S
is 0.9Ws per degree per gram for aluminum heat sinks.
Figure 8 shows the time to thermal shutdown versus power
dissipation for a part in +22
o
C still air and at various elevated
ambient temperatures with a
SA
of +27
o
C/W from forced air
flow.
For the shorter shutdown times, the
SA
value is not impor-
tant but the thermal capacitances are. A more accurate
equation for the transient silicon surface temperature can be
derived from the model shown in Figure 7. Due to the distrib-
uted nature of the package thermal capacitance, the second
time constant is 1.7 times larger than expected.
FIGURE 8. TIME TO THERMAL SHUTDOWN vs POWER
DISSIPATION
Thermal Shutdown Hysteresis
Figure 9 shows the HIP5600 thermal hysteresis curve with
V
IN
= 100V
DC
, V
OUT
= 5V and I
OUT
= 10mA. Hysteresis is
added to the thermal shutdown circuit to prevent oscillations
as the junction temperature approaches the thermal shut-
down limit. The thermal shutdown is reset when the input
voltage is removed, goes negative (i.e. AC operation) or
when the part cools down.
FIGURE 9. THERMAL HYSTERESIS CURVE
AC to DC Operation
Since the HIP5600 has internal high voltage diodes in series
with its input, it can be connected directly to an AC power
line. This is an improvement over typical low current supplies
constructed from a high voltage diode and voltage dropping
resistor to bias a low voltage zener. The HIP5600 provides
better line and load regulation, better efficiency and heat
T
J
t
( )
T
A
P
JC
P
SA
1 e
t
-----
+
+
=
SA
C
P
C
S
+
(
)
Where:
(EQ. 9)
t
ln
P
JC
SA
+
(
)
T
+
A
T
TS
P
SA
-------------------------------------------------------------------
=
(EQ. 10)
TIME T
O
THERMAL SHUTDO
WN (s)
POWER DISSIPATION (W)
+22
o
C
+70
o
C
+85
o
C
+115
o
C
+120
o
C
+100
o
C
10
2
10
1
10
0
10
-1
10
-2
0.0
2.0
4.0
6.0
8.0
10
T
J
t
( )
T
A
T
1
T
2
T
3
+
+
+
=
T
3
0.6P
JC
1 e
t
3
--------
T
2
0.4P
JC
1 e
t
2
--------
T
1
P
SA
1 e
t
1
--------
1
SA
C
P
C
S
+
(
)
2
0.7
JC
0.5C
P
C
S
+
(
)
0.5C
P
C
P
C
S
+
------------------------------------------------------------
3
0.6
JC
C
D
(EQ. 11C)
(EQ. 11D)
Where:
Where:
Where:
(EQ. 11B)
(EQ. 11A)
CASE TEMPERATURE (
o
C)
I
OUT
(mA)
HEATING
SHUTDOWN
REGION
COOLING
10
8.0
6.0
4.0
2.0
0.0
98.0
105.0
113.0
120
127
135
142
HIP5600
8
transfer. The latter because the TO-220 package permits
easy heat sinking.
The efficiency of either supply is approximately the DC
output voltage divided by the RMS input voltage. The
resistor value, in the typical low current supply, is chosen
such that for maximum load at minimum line voltage there is
some current flowing into the zener. This resistor value
results in excess power dissipation for lighter loads or higher
line voltages.
Using the circuit in Figure 3 with a 1000
F output capacitor
the HIP5600 only takes as much current from the power line
as the load requires. For light loads, the HIP5600 is even
more efficient due to it's interaction with the output capacitor.
Immediately after the AC line goes positive, the HIP5600
tries to replace all the charge drained by the load during the
negative half cycle at a rate limited by the short circuit cur-
rent limit (see "A1" and "B1" Figure 10). Since most of this
charge is replaced before the input voltage reaches its RMS
value, the power dissipation for this charge is lower than it
would be if the charge were transferred at a uniform rate dur-
ing the cycle. When the product of the input voltage and cur-
rent is averaged over a cycle, the average power is less than
if the input current were constant. Figure 11 shows the
HIP5600 efficiency as a function of load current for 80V
RMS
and 132V
RMS
inputs for a 15.6V output.
FIGURE 10. AC OPERATION
FIGURE 11. EFFICIENCY AS A FUNCTION OF LOAD CURRENT
Referring again to Figure 10, Curve "A1" shows the input
current for a 10mA output load and curve "B1" with a 3mA
output load. The input current spike just before the negative
going zero crossing occurs while the input voltage is less
than the minimum operating voltage but is so short it has no
detrimental effect. The input current also includes the charg-
ing current for the 0.02
F input decoupling capacitor C1.
The maximum load current cannot be greater than 1/2 of the
short circuit current because the HIP5600 only conducts over
1/2 of the line cycle. The short circuit current limit (Figure 38)
depends on the case temperature, which is a function of the
power dissipation. Figure 38 for a case temperature of
+100
o
C (i.e. no heat sink) indicates for AC operation the
maximum available output current is 10mA (1/2 x 20mA).
Operation from full wave rectified input will increase the
maximum output current to 20mA for the same +100
o
C case
temperature.
As a reminder, since the HIP5600 is off during the negative
half cycle, the output capacitor must be large enough to sup-
ply the maximum load current during this time with some
acceptable level of droop. Figure 10 also shows the output
ripple voltage, for both a 10mA and 3mA output loads "A2"
and "B2", respectively.
Do's And Don'ts
DC Operation
1. Do not exceed the absolute maximum ratings.
2. The HIP5600 requires a minimum output current of 1mA.
Minimum output current includes current through RF1.
Warning: If there is less than 1mA load current, the out-
put voltage will rise. If the possibility of no load exists,
RF1 should be sized to sink 1mA under these conditions.
3. Do not "HOT" switch the input voltage without protecting
the input voltage from exceeding
650V. Note: induc-
tance from supplies and wires along with the 0.02
F
decoupling capacitor can form an under damped tank cir-
cuit that could result in voltages which exceed the maxi-
mum
650V input voltage rating. Switch arcing can
further aggravate the effects of the source inductance
creating an over voltage condition.
Recommendation: Adequate protection means (such
as MOV, avalanche diode, surgector, etc.) may be
needed to clamp transients to within the
650V input limit
of the HIP5600.
4. Do not operate the part with the input voltage below the
minimum 50V
DC
recommended. Low voltage opera-
tion: For input voltages between 0V
DC
and +5V
DC
noth-
ing happens (I
OUT
= 0), for input voltages between
+5V
DC
and +35V
DC
there is not enough voltage for the
pass transistor to operate properly and therefore a high
frequency (2MHz) oscillation occurs. For input voltages
+35V
DC
to +50V
DC
proper operation can occur with
some parts.
I
IN
V
OUT
120V
RMS
, 60Hz
20mA/DIV.
A1
B1
B2
A2
100mV/DIV.
2ms/DIV.
EFFICIENCY (%)
LOAD CURRENT (mA)
V
IN
= 132V
RMS
V
IN
= 80V
RMS
V
OUT
= 15.6V
DC
25
23
19
21
18
16
14
12
10
0.0
5.0
10.0
15.0
RF1
MIN
REF
V
1mA
------------------
1.07V
1mA
----------------
1k
=
=
=
HIP5600
9
5. Warning: the output voltage will approach the input volt-
age if the adjust pin is disconnected, resulting in perma-
nent damage to the low voltage output capacitor.
AC Operation
1. Do not exceed the absolute maximum ratings.
2. The HIP5600 requires a minimum output current of
0.5mA. Minimum output current includes current through
RF1. Warning: If there is less than 0.5mA output current,
the output voltage will rise. If the possibility of no load
exists, RF1 should be sized to sink 0.5mA under these
conditions.
3. If using a laboratory AC source (such as VARIACs or
step-up transformers, etc.) be aware that they contain
large inductances that can generate damaging high volt-
age transients when they are switched on or off.
Recommendations
(1) Preset VARIAC output voltage before applying power
to part.
(2) Adequate protection means (such as MOV, avalanche
diode, surgector, etc.) may be needed to clamp tran-
sients to within the
650V input limit of the HIP5600.
4. Do not operate the part with the input voltage below the
minimum 50V
RMS
recommended. Low voltage opera-
tion similar to DC operation (reference step 4 under
DC operation).
5. Warning: the output voltage will approach the input volt-
age if the adjust pin is disconnected, resulting in perma-
nent damage to the low voltage output capacitor.
General Precautions
Instrumentation Effects
Background: Input to output parasitic impedances exist in
most test equipment power supplies. The inter-winding
capacitance of the transformer may result in substantial cur-
rent flow (mA) from the equipment power lines to the DC
ground of the HIP5600. This "ground loop" current can result
in erroneous measurements of the circuits performance and
in some cases lead to overstress of the HIP5600.
Recommendations for Evaluation of the HIP5600
in the Lab
a) The use of battery powered DVMs and scopes will elimi-
nate ground loops.
b) When connecting test equipment, locate grounds as
close to circuit ground as possible.
c) Input current measurements should be made with a non-
contact current probe.
If AC powered test equipment is used, then the use of an
isolated plug is recommended. The isolated plug eliminates
any voltage difference between earth ground and AC
ground. However, even though the earth ground is discon-
nected, ground loop currents can still flow through trans-
former of the test equipment. Ground loops can be
minimized by connecting the test equipment ground as
close to the circuit ground as possible.
CAUTION:
Dangerous voltages may appear on exposed
metal surfaces of AC powered test equipment.
Application Circuits
FIGURE 12. DC/DC CONVERTER
The HIP5600 can be configured in most common DC linear
regulator applications circuits with an input voltage between
50V
DC
to 400V
DC
(above the output voltage) see Figure 12.
A 10
F capacitor (C2) provides stabilization of the output
stage. Heat sinking may be required depending upon the
power dissipation. Normally, choose RF1 << V
REF
/I
ADJ
.
FIGURE 13. AC/DC CONVERTER
The HIP5600 can operate from an AC voltage between
50V
RMS
to 280V
RMS
, see Figure 13. The combination of a
1k
(2W) input resistor and a V275LA10B MOV provides
input surge protection up to 6kV 1.2 x 50
s oscillating and
pulse waveforms as defined in IEEE/ANSI C62.41.1980.
When operating from 120V
AC
, a V130LA10B MOV provides
protection without the 1k
resistor.
The output capacitor is larger for operation from AC than DC
because the HIP5600 only conducts current during the posi-
tive half cycle of the AC line. The efficiency is approximately
equal to V
OUT
/V
IN
(RMS), see Figure 11.
RF1
MIN
REF
V
0.5mA
------------------
1.07V
0.5mA
------------------
2k
=
=
=
+ 50VDC TO 400VDC BUS
ADJ
V
OUT
V
IN
+ V
OUT
RF1
RF2
C1
0.02
F
C2
C3
10
F
HIP5600
10
F
SURGE
PROTECTION
NOTE 1. 200V
RMS
- 280V
RMS
ADJ
V
OUT
V
IN
+ V
OUT
RF1
RF2
C1
0.02
F
C2
HIP5600
10
F
Operation Only
C3
10
F
1k
(NOTE 1)
HIP5600
10
The HIP5600 provides an efficient and economical solution
as a start-up supply for applications operating from either AC
(50V
RMS
to 280V
RMS
) or DC (50V
DC
to 400V
DC
).
FIGURE 14. START UP CIRCUIT
The HIP5600 has on chip thermal protection and output cur-
rent limiting circuitry. These features eliminate the need for
an in-line fuse and a large heat sink.
The HIP5600 can provide up to 40mA for short periods of time
to enable start up of a switch mode power supply`s control cir-
cuit. The length of time that the HIP5600 will be on, prior to
thermal shutdown, is a function of the power dissipation in the
part, the amount of heat sinking (if any) and the ambient tem-
perature. For example; at 400V
DC
with no heat sink, it will pro-
vide 20mA for about 8s, see Figure 8.
Power supply efficiency is improved by turning off the
HIP5600 when the SMPS is up and running. In this applica-
tion the output of the HIP5600 would be set via RF1 and RF2
to be about 9V. The tickler winding would be adjusted to about
12V to insure that the HIP5600 is kept off during normal oper-
ating conditions.The input current under these conditions is
approximately equal to I
BIAS
. (See Figure 27)
.
The HIP5600 can supply a 450
A (
20%) constant current.
(See Figure 15). It makes use of the internal bias network.
See Figure 27 for bias current versus input voltage.
With the addition of a potentiometer and a 10
F capacitor the
HIP5600 will provide a constant current source. I
OUT
is given
by Equation 13 in Figure 16.
The HIP5600 can control a P-channel MOSFET or IGPT in a
self-oscillating buck regulator. The circuit shown (Figure 17)
shows the self-oscillating concept with a P-IGBT driving a
dedicated fan load. The output voltage is set by the resistor
combination of RF1, RF2, and RF3. Components C3 and
RF3 impresses the output ripple voltage across RF1 causing
the HIP5600 to oscillate and control the conduction of the
P-IGBT. The start-up protection components limit the initial
surge current in the P-IGBT by forcing this device into its
active region. The snubber circuit is recommended to reduce
the power dissipation of the P-IGBT.
V
OUT
+ 50V
DC
TO 400V
DC
ADJ
V
OUT
V
IN
RF1
RF2
HIP5600
10
F
BUS
PWM
+12V
FIGURE 15. CONSTANT 450
A CURRENT SOURCE
FIGURE 16. ADJUSTABLE CURRENT SOURCE
+20V
DC
TO +400V
DC
I
OUT
ADJ
V
OUT
V
IN
HIP5600
LOAD
NOTES:
1. V
OUT
Floating
2. Fixed 500
A Current Source
ADJ
V
OUT
V
IN
I
OUT
0.02
F
HIP5600
10
F
I
OUT
=1.21V
R1
(EQ. 13)
R1
+50V
DC
TO +400V
DC
HIP5600
11
FIGURE 17. HIGH CURRENT "BUCK" REGULATOR CONCEPT
RF3
C3
P-IGBT
RF1
RF2
START-UP PROTECTION
SNUBBER CIRCUIT
DC
FAN
ADJ
V
OUT
V
IN
HIP5600
+
-
Typical Performance Curves
FIGURE 18. LOAD REGULATION vs TEMPERATURE
FIGURE 19. LOAD REGULATION VS. TEMPERATURE
FIGURE 20. RIPPLE REJECTION RATIO (OUTPUT VOLTAGE)
FIGURE 21. RIPPLE REJECTION RATIO (OUTPUT VOLTAGE)
-1.6
-1.4
-1.2
-1.0
-0.8
-0.6
-0.4
CASE TEMPERATURE (
o
C)
OUTPUT V
O
L
T
A
GE DEVIA
TION (%)
-40
-20
0
25
40
60
80
100
1mA TO 20mA
1mA TO 30mA
1mA TO 10mA
V
IN
= 50V
DC
-10
-9
-8
-7
-6
-5
-4
-3
-2
-1
CASE TEMPERATURE (
o
C)
OUTPUT V
O
L
T
A
GE DEVIA
TION (%)
-40
-20
0
25
40
60
80
1mA TO 10mA
1mA TO 20mA
1mA TO 30mA
V
IN
= 400V
DC
0
10
20
30
40
50
60
70
80
90
100 110
45
50
55
60
65
70
75
80
85
OUTPUT VOLTAGE (V)
RIPPLE REJECTION (dB)
V
IN
= 170V
DC
, I
L
= 10mA, f = 120Hz, T
C
= +25
o
C
1
F BYPASS CAPACITOR
10
F BYPASS CAPACITOR
NO BYPASS CAPACITOR
0
50
100
150
200
250
300
350
30
40
50
60
70
80
90
OUTPUT VOLTAGE (V)
RIPPLE REJECTION (dB)
V
IN
= 400V
DC
, I
L
= 10mA, f = 120Hz, T
C
= +25
o
C
1
F BYPASS CAPACITOR
NO BYPASS CAPACITOR
10
F BYPASS CAPACITOR
HIP5600
12
FIGURE 22. RIPPLE REJECTION RATIO (INPUT FREQUENCY)
FIGURE 23. RIPPLE REJECTION RATIO (INPUT FREQUENCY)
FIGURE 24. RIPPLE REJECTION RATIO (OUTPUT CURRENT)
FIGURE 25. RIPPLE REJECTION RATIO (OUTPUT CURRENT)
FIGURE 26. OUTPUT IMPEDANCE
FIGURE 27. IBIAS vs INPUT VOLTAGE
Typical Performance Curves
(Continued)
1
10
100
1k
10k
100k
1M
45
50
55
60
65
70
75
80
85
INPUT FREQUENCY (Hz)
10M
RIPPLE REJECTION (dB)
V
IN
= 170V
DC
, I
L
= 10mA, V
OUT
= 15V, T
C
= +25
o
C
1
F BYPASS CAPACITOR
10
F BYPASS
NO BYPASS CAPACITOR
CAPACITOR
45
50
55
60
65
70
75
80
85
INPUT FREQUENCY (Hz)
1
10
100
1k
10k
100k
1M
10M
RIPPLE REJECTION (dB)
V
IN
= 400V
DC
, I
L
= 10mA, V
OUT
= 15V, T
C
= +25
o
C
1
F BYPASS CAPACITOR
10
F BYPASS
NO BYPASS CAPACITOR
CAPACITOR
0
5
10
15
20
25
30
35
50
55
60
65
70
75
80
85
OUTPUT CURRENT (mA)
RIPPLE REJECTION (dB)
V
IN
= 170V
DC
, V
OUT
= 10mA, f = 120Hz, T
C
= +25
o
C
(REFERENCE FIGURE 3)
NO BYPASS CAPACITOR
1
F BYPASS CAPACITOR
10
F BYPASS CAPACITOR
0
5
10
15
20
25
30
35
50
55
60
65
70
75
80
85
OUTPUT CURRENT (mA)
RIPPLE REJECTION (dB)
V
IN
= 400V
DC
, V
OUT
= 10mA, f = 120Hz, T
C
= +25
o
C
(REFERENCE FIGURE 3)
NO BYPASS CAPACITOR
10
F BYPASS CAPACITOR
1
F BYPASS CAPACITOR
0.1
1.0
10.0
100
FREQUENCY (Hz)
OUTPUT IMPED
ANCE (
)
10
100
1K
10K
100K
1M
C2 = 0.01
F, C3 = 0
F
C2 = 10
F, C3 = 0
F
C2 = 10
F, C3 = 10
F
420
430
440
450
460
470
480
490
500
510
520
I
OUT
= 0
INPUT VOLTAGE (V
DC
)
I
BIAS
(
A)
T
C
= -40
o
C
T
C
= +25
o
C
T
C
= +100
o
C
50
100
200
300
400
HIP5600
13
FIGURE 28. LINE TRANSIENT RESPONSE
FIGURE 29. LOAD TRANSIENT RESPONSE
FIGURE 30. REFERENCE VOLTAGE vs TEMPERATURE
FIGURE 31. REFERENCE VOLTAGE vs TEMPERATURE
FIGURE 32. REFERENCE VOLTAGE vs INPUT VOLTAGE
FIGURE 33. REFERENCE VOLTAGE vs V
IN
; CASE TEMPERA-
TURE OF +25
o
C
Typical Performance Curves
(Continued)
0V
100V
400V
INPUT
VOLTAGE
V
OUT
15V
C3 = 10
F
100mV/DIV
C3 = 0
F
V
OUT
= 15V
DC
I
L
= 5mA
T
J
= +25
o
C
T = 100ms/DIV
100V/DIV
15V
V
OUT
C3 = 10
F
20mV/DIV
0mA
10mA
5mA
OUTPUT CURRENT
T= 100ms/DIV
5mA/DIV
C3 = 0
F
V
IN
= 400V
DC
V
OUT
= 15V
T
J
= +25
o
C
1.10
1.11
1.12
1.13
1.14
1.15
1.16
1.17
1.18
1.19
1.20
1.21
CASE TEMPERATURE (
o
C)
REFERENCE V
O
L
T
A
GE (V)
1mA
5mA
-40
-20
0
25
40
60
80
100
20mA
30mA
10mA
V
IN
= 50V
DC
1.00
1.05
1.10
1.15
1.20
1.25
CASE TEMPERATURE (
o
C)
REFERENCE V
O
L
T
A
GE (V)
1mA
5mA
10mA
30mA
-40
-20
0
25
40
60
80
20mA
V
IN
= 400V
DC
0
100
200
300
400
1.08
1.09
1.10
1.11
1.12
1.13
1.14
1.15
1.16
1.17
1.18
1.19
1.20
INPUT VOLTAGE (V
DC
)
REFERENCE V
O
L
T
A
GE (V)
T
C
= -40
o
C
T
C
= +25
o
C
T
C
= +100
o
C
I
OUT
= 10mA
0
100
200
300
400
1.04
1.06
1.08
1.10
1.12
1.14
1.16
1.18
1.20
INPUT VOLTAGE (V
DC
)
REFERENCE V
O
L
T
A
GE (V)
1mA
10mA
20mA
30mA
5mA
HIP5600
14
FIGURE 34. I
ADJ
vs TEMPERATURE
FIGURE 35. I
ADJ
vs TEMPERATURE
FIGURE 36. MINIMUM LOAD CURRENT vs V
IN
FIGURE 37. TERMINAL CURRENTS vs FORCED V
REF
FIGURE 38. CURRENT LIMIT vs TEMPERATURE
Typical Performance Curves
(Continued)
45
50
55
60
65
70
75
80
CASE TEMPERATURE (
o
C)
ADJ CURRENT (
A)
1mA
30mA
-40
-20
0
25
40
60
80
100
V
IN
= 50V
DC
20mA
45
50
55
60
65
70
75
80
CASE TEMPERATURE (
o
C)
ADJ CURRENT (
A)
1mA
5mA
10mA
-40
-20
0
25
40
60
80
V
IN
= 400V
DC
20mA
30mA
745
750
755
760
765
770
775
INPUT VOLTAGE (V
DC
)
LOAD CURRENT (
A)
T
C
= +25
o
C
T
C
= +100
o
C
50
100
200
300
400
1
2
3
4
5
0
500
1000
1500
2000
V
OUT
- V
ADJ
CURRENT (
A)
I
IN
I
OUT
I
ADJ
(V
DC
)
MINIMUM LOAD
CURRENT
V
IN
= 100V
DC
T
C
= 25
o
C
BIAS CURRENT
20
25
30
35
40
45
50
55
INPUT-OUTPUT (V
DC
)
OUTPUT CURRENT (mA)
50
100
150
200
250
300
350
400
T
C
= -40
o
C
T
C
= +25
o
C
T
C
= +100
o
C
HIP5600
15
Evaluation Boards
FIGURE 39. EVALUATION BOARD (TOP)
FIGURE 40. EVALUATION BOARD METAL MASK (BOTTOM)
FIGURE 41. EVALUATION BOARD METAL MASK (TOP)
ADJ
V
IN
V
OUT
HIP5600 EVALUATION BOARD
F1
V
IN
V
OUT
RF1
C2
C3
RF2
C1
MOV
R
S
-
+
HEAT SINK
3.25"
3.25"
SA
= 22
o
C/W
HIP5600
3.25"
3.25"
ADJ
V
IN
V
OUT
HIP5600 EVALUATION BOARD
V
IN
V
OUT
-
+
HEAT SINK
3.25"
3.25"
HIP5600
16
HIP5600
Single-In-Line Plastic Packages (SIP)
NOTES:
1. Lead dimension and finish uncontrolled in zone L1.
2. Position of lead to be measured 0.250 inches (6.35mm) from bot-
tom of dimension D.
3. Position of lead to be measured 0.100 inches (2.54mm) from bot-
tom of dimension D.
4. Controlling dimension: INCH.
E
P
Q
D
H1
L
L1
b
1
b
1
2
3
e
e
1
A
c
1
J1
F
Z3.1B
3 LEAD PLASTIC SINGLE-IN-LINE PACKAGE
SYMBOL
INCHES
MILLIMETERS
NOTES
MIN
MAX
MIN
MAX
A
0.140
0.190
3.56
4.82
-
b
0.015
0.040
0.38
1.02
-
b1
0.045
0.070
1.14
1.77
1
c1
0.014
0.022
0.36
0.56
1
D
0.560
0.650
14.23
16.51
-
E
0.380
0.420
9.66
10.66
-
e
0.090
0.110
2.29
2.79
2
e1
0.190
0.210
4.83
5.33
2
F
0.020
0.055
0.51
1.39
-
H1
0.230
0.270
5.85
6.85
-
J1
0.080
0.115
2.04
2.92
3
L
0.500
0.580
12.70
14.73
-
L1
-
0.250
-
6.35
1
P
0.139
0.161
3.53
4.08
-
Q
0.100
0.135
2.54
3.43
-
Rev. 1 2/95
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