2002 Microchip Technology Inc.

DS21344B-page 1

Features

· Tiny SOT-23A Packages

· Optimized for Single Supply Operation

· Ultra Low Input Bias Current: Less than 100pA

· Low Quiescent Current: 4

A (TC1037),

Shutdown Mode: 4

A, 0.05

A (TC1038),

A (TC1039)

· Shutdown Mode (TC1038)

· 2.0% Accurate Independent Voltage Reference

(TC1039)

· Rail-to-Rail Inputs and Outputs

· Operation Down to V

= 1.8V

Applications

· Power Management Circuits

· Battery Operated Equipment

· Consumer Products

Device Selection Table

Package Types

General Description

The TC1037/TC1038/TC1039 are single, low-power
comparators designed for low-power applications.

These comparators are specifically designed for
operation from a single supply. However, operation
from dual supplies also is possible, and power supply
current is independent of the magnitude of the power
supply voltage. The TC1037/TC1038/TC1039 operate
from two 1.5V alkaline cells down to V

= 1.8V. Active

supply current is 4

A for the TC1037/TC1038 and 6

for the TC1039. Input and output swing of these
devices is rail-to-rail.

An active low shutdown input, SHDN, is available on
the TC1038 and disables the comparator, placing its
output in a high-impedance state. The TC1038 draws
only 0.05

A (typical) when the shutdown mode is

active.

An internally biased 1.20V bandgap reference is
included in the TC1039. The reference is accurate to
2.0 percent tolerance. This reference is independent of
the comparator in the TC1039.

Packaged in a 5-Pin SOT-23A (TC1037) or 6-Pin
SOT-23A (TC1038/TC1039), these single comparators
are ideal for applications requiring high integration,
small size and low power.

Functional Block Diagram

Part Number

Package

Temperature

Range

TC1037CECT

5-Pin SOT-23A

-40°C to +85°C

TC1038CECH

6-Pin SOT-23A

-40°C to +85°C

TC1039CECH

6-Pin SOT-23A

-40°C to +85°C

OUTPUT

IN+

IN-

5-Pin SOT-23A

TC1037ECT

OUTPUT

IN+

IN-

SHDN

6-Pin SOT-23A

TC1038ECH

OUTPUT

IN+

IN-

REF

6-Pin SOT-23A

TC1039ECH

NOTE: 5-Pin SOT-23A is equivalent to the EIAJ SC-74A.

6-Pin SOT-23A is equivalent to the EIAJ SC-74.

OUTPUT

IN+

TC1037

OUTPUT

IN+

TC1038

IN-

SHDN

IN-

OUTPUT

IN+

TC1039

Voltage

Reference

IN-

REF

TC1037/TC1038/TC1039

Linear Building Block Single Comparator in SOT Packages

TC1037/TC1038/TC1039

DS21344B-page 2

2002 Microchip Technology Inc.

1.0

ELECTRICAL
CHARACTERISTICS

ABSOLUTE MAXIMUM RATINGS*

Supply Voltage ......................................................6.0V

Voltage on Any Pin .......... (V

0.3V) to (V

+ 0.3V)

Junction Temperature....................................... +150°C

Operating Temperature Range............. -40°C to +85°C

Storage Temperature Range .............. -55°C to +150°C

*Stresses above those listed under "Absolute Maximum
Ratings" may cause permanent damage to the device. These
are stress ratings only and functional operation of the device
at these or any other conditions above those indicated in the
operation sections of the specifications is not implied.
Exposure to Absolute Maximum Rating conditions for
extended periods may affect device reliability.

TC1037/TC1038/TC1039 ELECTRICAL SPECIFICATIONS

Electrical Characteristics: Typical values apply at 25°C and V

= 3.0V. Minimum and maximum values apply for T

= -40° to

+85°C and V

= 1.8V to 5.5V, unless otherwise specified.

Symbol

Parameter

Min

Typ

Max

Units

Test Conditions

Supply Voltage

1.8

5.5

Supply Current, Operating (TC1039)
(TC1037/TC1038)

--
--

6
4

All Outputs Unloaded,
SHDN = V

for TC1038

SHDN

Supply Current Shutdown Mode
(TC1038 Only)

0.3

SHDN = V

Shutdown Input (TC1038 Only)

Input High Threshold

80% V

Input Low Threshold

20% V

Shutdown Input Current

±100

Comparator

OUT

(SD)

Output Resistance in Shutdown

SHDN = V

(TC1038 Only)

OUT

(SD)

Output Capacitance in Shutdown

SHDN = V

(TC1038 Only)

SEL

Select Time

sec

OUT

Valid from SHDN = V

= 10k

to V

(TC1038 Only)

DESEL

Deselect Time

500

nsec

OUT

Valid from SHDN = V

= 10k

to V

ICMR

Common Mode Input Voltage Range V

0.2

+ 0.2

VOL

Large Signal Voltage Gain

100

V/mV

= 10k

, V

= 5V

GBWP

Gain Bandwidth Product

kHz

= 1.8V to 5.5V;

= V

to V

Input Offset Voltage

5
5

+5
+5

mV
mV

= 3V, V

= 1.5V, T

= 25°C,

= -40°C to 85°C

Input Bias Current

±100

= 25°C;

IN+, IN- = V

to V

Output High Voltage

0.3

= 10k

to V

Output Low Voltage

0.3

= 10k

to V

CMRR

Common Mode Rejection Ratio

= 25°C; V

= 5V;

= V

to V

PSRR

Power Supply Rejection Ratio

= 25°C; V

= 1.2V;

= 1.8V to 5V

SRC

Output Source Current

IN+ = V

, IN- = V

Output Shorted to V

= 1.8V

SINK

Output Sink Current

IN+ = V

, IN- = V

Output Shorted to V

= 1.8V

PD1

Response Time

sec

100mV Overdrive, C

= 100pF

PD2

Response Time

sec

10mV Overdrive, C

= 100pF

TC1037/TC1038/TC1039

DS21344B-page 4

2002 Microchip Technology Inc.

2.0

PIN DESCRIPTIONS

The description of the pins are listed in Table 2-1.

TABLE 2-1:

PIN FUNCTION TABLE

Pin No.

TC1037

(5-Pin SOT-23A)

Symbol

Description

OUTPUT

Comparator output.

Negative power supply.

IN+

Comparator non-inverting input.

IN-

Comparator inverting input.

Positive power supply.

Pin No.

TC1038

(6-Pin SOT-23A)

Symbol

Description

OUTPUT

Comparator output.

Negative power supply.

IN+

Comparator non-inverting input.

IN-

Comparator inverting input.

SHDN

Active low shutdown input (TC1038 only). A low input on this pin disables the comparator
and places the output terminal in a high impedance state.

Positive power supply.

Pin No.

TC1039

(6-Pin SOT-23A)

Symbol

Description

OUTPUT

Comparator output.

Negative power supply.

IN+

Comparator non-inverting input.

IN-

Comparator inverting input.

REF

1.20V bandgap voltage reference output (TC1039 only).

Positive power supply.

2002 Microchip Technology Inc.

DS21344B-page 5

TC1037/TC1038/TC1039

3.0

DETAILED DESCRIPTION

The TC1037/TC1038/TC1039 are a series of very low
power, linear building block products targeted at low
voltage, single supply applications. The TC1037/
TC1038/TC1039 minimum operating voltage is 1.8V
and typical supply current is only 4

A for the TC1037

and TC1038 (fully enabled) and 6

A for the TC1039.

3.1

Comparator

The

TC1037/8/9

contain

one

comparator.

The

comparator's input range extends beyond both supply
voltages by 200mV and the outputs will swing to within
several millivolts of the supplies depending on the load
current being driven.

The comparator exhibits a propagation delay and
supply current which is largely independent of supply
voltage. The low input bias current and offset voltage
makes it suitable for high impedance precision
applications.

The TC1038 comparator is disabled during shutdown
and has a high impedance output.

3.2

Voltage Reference

A 2.0% tolerance, internally biased, 1.20V bandgap
voltage reference is included in the TC1039. It has a
push-pull output capable of sourcing and sinking at
least 50

3.3

Shutdown Input (TC1038 Only)

SHDN at V

disables the comparator and reduces the

supply current to less than 0.3

A. The SHDN input

cannot be allowed to float. When not used, connect it to
V

. The comparator's output is in a high impedance

state when the TC1038 is disabled. The comparator's
inputs can be driven from rail-to-rail by an external
voltage when the TC1038 is disabled. No latchup will
occur when the device is driven to its enabled state
when SHDN is set to V

4.0

TYPICAL APPLICATIONS

The TC1037/TC1038/TC1039 family lends itself to a
wide variety of applications, particularly in battery
powered systems. It typically finds application in power
management, processor supervisory and interface
circuitry.

4.1

External Hysteresis (Comparator)

Hysteresis can be set externally with two resistors
using positive feedback techniques (see Figure 4-1).
The design procedure for setting external comparator
hysteresis is as follows:

Choose the feedback resistor R

. Since the

input bias current of the comparator is at most
100pA, the current through R

can be set to

100nA (i.e., 1000 times the input bias current)
and retain excellent accuracy. The current
through R

at the comparator's trip point is V

where V

is a stable reference voltage.

Determine the hysteresis voltage (V

) between

the upper and lower thresholds.

Calculate R

as follows:

EQUATION 4-1:

Choose the rising threshold voltage for V

SRC

THR

Calculate R

as follows:

EQUATION 4-2:

Verify

the

threshold

voltages

with

these

formulas:

SRC

rising:

EQUATION 4-3:

SRC

falling:

EQUATION 4-4:

-----------

THR

---------------------

-------

-----------------------------------------------------------

TH R

(

)

(

)

-------

THF

THR

-------------------------

TC1037/TC1038/TC1039

DS21344B-page 6

2002 Microchip Technology Inc.

4.2

Precision Battery Monitor

Figure 4-2 is a precision battery low/battery dead
monitoring circuit. Typically, the battery low output
warns the user that a battery dead condition is
imminent. Battery dead typically initiates a forced
shutdown to prevent operation at low internal supply
voltages (which can cause unstable system operation).

The circuit in Figure 4-2 uses a TC1034, a TC1037 and
a TC1039, and only six external resistors. AMP 1 is a
simple buffer, while CMPTR1 and CMPTR2 provide
precision voltage detection using V

as a reference.

Resistors R2 and R4 set the detection threshold for
BATT LOW, while resistors R1 and R3 set the detection
threshold for BATT FAIL. The component values shown
assert BATT LOW at 2.2V (typical) and BATT FAIL at
2.0V (typical). Total current consumed by this circuit is
typically 16

A at 3V. Resistors R5 and R6 provide

hysteresis for comparators CMPTR1 and CMPTR2,
respectively.

4.3

32.768 kHz "Time Of Day Clock"
Crystal Controlled Oscillator

A very stable oscillator driver can be designed by using
a crystal resonator as the feedback element. Figure 4-3
shows a typical application circuit using this technique
to develop a clock driver for a Time Of Day (TOD) clock
chip. The value of R

and R

determine the DC voltage

level at which the comparator trips in this case one-
half of V

. The RC time constant of R

and C

should

be set several times greater than the crystal oscillator's
period, which will ensure a 50% duty cycle by maintain-
ing a DC voltage at the inverting comparator input
equal to the absolute average of the output signal.

4.4

Non-Retriggerable One Shot
Multivibrator

Using two comparators, a non-retriggerable one shot
multivibrator can be designed using the circuit configu-
ration of Figure 4-4. A key feature of this design is that
the pulse width is independent of the magnitude of the
supply voltage because the charging voltage and the
intercept voltage are a fixed percentage of V

. In

addition, this one shot is capable of pulse width with as
much as a 99% duty cycle and exhibits input lockout to
ensure that the circuit will not re-trigger before the
output pulse has completely timed out. The trigger level
is the voltage required at the input to raise the voltage
at node A higher than the voltage at node B, and is set
by the resistive divider R4 and R10 and the impedance
network composed of R1, R2 and R3. When the one
shot has been triggered, the output of CMPTR2 is high,
causing the reference voltage at the non-inverting input
of CMPTR1 to go to V

. This prevents any additional

input pulses from disturbing the circuit until the output
pulse has timed out.

The value of the timing capacitor C1 must be small
enough to allow CMPTR1 to discharge C1 to a diode
voltage before the feedback signal from CMPTR2
(through R10) switches CMPTR1 to its high state and
allows C1 to start an exponential charge through R5.
Proper circuit action depends upon rapidly discharging
C1 through the voltage set by R6, R9 and D2 to a final
voltage of a small diode drop. Two propagation delays
after the voltage on C1 drops below the level on the
non-inverting input of CMPTR2, the output of CMPTR1
switches to the positive rail and begins to charge C1
through R5. The time delay which sets the output pulse
width results from C1 charging to the reference voltage
set by R6, R9 and D2, plus four comparator propaga-
tion delays. When the voltage across C1 charges
beyond the reference, the output pulse returns to
ground and the input is again ready to accept a trigger
signal.

4.5

Oscillators and Pulse Width
Modulators

Microchip's linear building block comparators adapt
well to oscillator applications for low frequencies (less
than 100kHz). Figure 4-5 shows a symmetrical square
wave generator using a minimum number of compo-
nents. The output is set by the RC time constant of R4
and C1, and the total hysteresis of the loop is set by R1,
R2 and R3. The maximum frequency of the oscillator is
limited only by the large signal propagation delay of the
comparator in addition to any capacitive loading at the
output which degrades the slew rate.

To analyze this circuit, assume that the output is initially
high. For this to occur, the voltage at the inverting input
must be less than the voltage at the non-inverting input.
Therefore, capacitor C1 is discharged. The voltage at
the non-inverting input (V

) is:

EQUATION 4-5:

where, if R1 = R2 = R3, then:

EQUATION 4-6:

R2 V

(

)

(

)

[

]

---------------------------------------------

2 V

(

)

-------------------

2002 Microchip Technology Inc.

DS21344B-page 7

TC1037/TC1038/TC1039

Capacitor C1 will charge up through R4. When the
voltage of the comparator's inverting input is equal to
V

, the comparator output will switch. With the output

at ground potential, the value at the non-inverting input
terminal (V

) is reduced by the hysteresis network to a

value given by:

EQUATION 4-7:

Using the same resistors as before, capacitor C1 must
now discharge through R4 toward ground. The output
will return to a high state when the voltage across the
capacitor has discharged to a value equal to V

. The

period of oscillation will be twice the time it takes for the
RC circuit to charge up to one half its final value. The
period can be calculated from:

EQUATION 4-8:

The frequency stability of this circuit should only be a
function of the external component tolerances.

Figure 4-6 shows the circuit for a pulse width modulator
circuit. It is essentially the same as in Figure 4-5 with
the addition of an input control voltage. When the input
control voltage is equal to one-half V

, operation is

basically the same as described for the free-running
oscillator. If the input control voltage is moved above or
below one-half V

, the duty cycle of the output square

wave will be altered. This is because the addition of the
control voltage at the input has now altered the trip
points. The equations for these trip points are shown in
Figure 4-6 (see V

and V

Pulse width sensitivity to the input voltage variations
can be increased by reducing the value of R6 from
10K

and conversely, sensitivity will be reduced by

increasing the value of R6. The values of R1 and C1
can be varied to produce the desired center frequency.

FIGURE 4-1:

COMPARATOR
EXTERNAL HYSTERESIS
CONFIGURATION

FIGURE 4-2:

PRECISION BATTERY MONITOR

-----------

FREQ

-----------------

2 0.694

(

)

(

)

(

)

OUT

SRC

TC1037

R2, 330k, 1%

TC1034

R4, 470k, 1%

R5, 7.5M

R6, 7.5M

R3, 470k, 1%

R1, 270k, 1%

To System DC/DC

Converter

Alkaline

TC1039

BATTFAIL

BATTLOW

CMPTR1

CMPTR2

AMP1

TC1037

TC1039

TC1037/TC1038/TC1039

DS21344B-page 10

2002 Microchip Technology Inc.

5.0

TYPICAL CHARACTERISTICS

Note:

The graphs and tables provided following this note are a statistical summary based on a limited number of
samples and are provided for informational purposes only. The performance characteristics listed herein
are not tested or guaranteed. In some graphs or tables, the data presented may be outside the specified
operating range (e.g., outside specified power supply range) and therefore outside the warranted range.

1.5

2.5

3.5

4.5

5.5

SUPPLY VOLTAGE (V)

Comparator Propagation Delay

vs. Supply Voltage

DELAY TO RISING EDGE (

sec)

Overdrive = 10mV

Overdrive = 50mV

1.5

2.5

3.5

4.5

5.5

DELAY TO FALLING EDGE (

sec)

-40

°C

TEMPERATURE (

°C)

DELAY TO RISING EDGE (

sec)

Overdrive = 100mV

Overdrive = 10mV

Overdrive = 50mV

Comparator Propagation Delay

vs. Supply Voltage

Comparator Propagation Delay

vs. Temperature

= 25°C

= 100pF

= 25°C

= 100pF

Overdrive = 100mV

= 4V

= 5V

= 2V

= 3V

-40

°C

2.5

2.0

1.5

1.0

- V

OUT

(V)

SOURCE

(mA)

Comparator Output Swing
vs. Output Source Current

DELAY TO FALLING EDGE (

sec)

Overdrive = 100mV

2.5

2.0

1.5

1.0

Comparator Propagation Delay

vs. Temperature

Comparator Output Swing

vs. Output Sink Current

TEMPERATURE (

°C)

SINK

(mA)

= 4V

= 5V

= 2V

= 3V

= 25°C

= 3V

= 1.8V

= 5.5V

= 3V

= 1.8V

= 5.5V

OUT

- V

(V)

Sinking

OUTPUT SHORT-CIRCUIT CURRENT (mA)

SUPPLY VOLTAGE (V)

Comparator Output Short-Circuit

Current vs. Supply Voltage

Sourcing

= -40

= 25

= 85

= 25

= 85

REFERENCE VOLTAGE (V)

1.240

1.220

1.200

1.180

1.160

1.140

LOAD CURRENT (mA)

Reference Voltage vs.

Load Current

= 1.8V

= 3V

= 5.5V

Sinking

Sourcing

= 1.8V

= 3V

= 5.5V

100

200

300

400

SUPPLY AND REFERENCE VOLTAGES (V)

TIME (

µsec)

Line Transient

Response of V

REF

2002 Microchip Technology Inc.

DS21344B-page 17

TC1037/TC1038/TC1039

Information contained in this publication regarding device
applications and the like is intended through suggestion only
and may be superseded by updates. It is your responsibility to
ensure that your application meets with your specifications.
No representation or warranty is given and no liability is
assumed by Microchip Technology Incorporated with respect
to the accuracy or use of such information, or infringement of
patents or other intellectual property rights arising from such
use or otherwise. Use of Microchip's products as critical com-
ponents in life support systems is not authorized except with
express written approval by Microchip. No licenses are con-
veyed, implicitly or otherwise, under any intellectual property
rights.

Trademarks

The Microchip name and logo, the Microchip logo, FilterLab,
K

, microID,

MPLAB, PIC, PICmicro, PICMASTER,

PICSTART, PRO MATE, SEEVAL and The Embedded Control
Solutions Company are registered trademarks of Microchip Tech-
nology Incorporated in the U.S.A. and other countries.

dsPIC, ECONOMONITOR, FanSense, FlexROM, fuzzyLAB,
In-Circuit Serial Programming, ICSP, ICEPIC, microPort,
Migratable Memory, MPASM, MPLIB, MPLINK, MPSIM,
MXDEV, PICC, PICDEM, PICDEM.net, rfPIC, Select Mode
and Total Endurance are trademarks of Microchip Technology
Incorporated in the U.S.A.

Serialized Quick Turn Programming (SQTP) is a service mark
of Microchip Technology Incorporated in the U.S.A.

All other trademarks mentioned herein are property of their
respective companies.

Printed on recycled paper.

Microchip received QS-9000 quality system
certification for its worldwide headquarters,
design and wafer fabrication facilities in
Chandler and Tempe, Arizona in July 1999
and Mountain View, California in March 2002.
The Company's quality system processes and
procedures are QS-9000 compliant for its
PICmicro

8-bit MCUs, K

code hopping

devices, Serial EEPROMs, microperipherals,
non-volatile memory and analog products. In
addition, Microchip's quality system for the
design and manufacture of development
systems is ISO 9001 certified.

DS21344B-page 18

2002 Microchip Technology Inc.

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Parc d'Activite du Moulin de Massy
43 Rue du Saule Trapu
Batiment A - ler Etage
91300 Massy, France
Tel: 33-1-69-53-63-20 Fax: 33-1-69-30-90-79

Germany

Microchip Technology GmbH
Gustav-Heinemann Ring 125
D-81739 Munich, Germany
Tel: 49-89-627-144 0 Fax: 49-89-627-144-44

Italy

Microchip Technology SRL
Centro Direzionale Colleoni
Palazzo Taurus 1 V. Le Colleoni 1
20041 Agrate Brianza
Milan, Italy
Tel: 39-039-65791-1 Fax: 39-039-6899883

United Kingdom

Arizona Microchip Technology Ltd.
505 Eskdale Road
Winnersh Triangle
Wokingham
Berkshire, England RG41 5TU
Tel: 44 118 921 5869 Fax: 44-118 921-5820

03/01/02

*DS21344B*

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