NCP1509
Semiconductor Components Industries, LLC, 2004
September, 2004 - Rev. 0
1
Publication Order Number:
NCP1509/D
NCP1509
Up to 500 mA, 1 MHz, High
Efficiency Synchronous
Step-Down DC-DC
Converter in DFN Package
The NCP1509 step-down PWM DC-DC converter is optimized
for portable applications powered from 1-cell Li-ion or 3 cell
Alkaline/NiCd/NiMH batteries. This DC-DC converter utilizes a
current-mode control architecture for easy compensation and better
line regulation. It also uses synchronous rectification to increase
efficiency and reduce external part count. The NCP1509 optimizes
efficiency in light load conditions when switched from a normal
PWM mode to a "pulsed switching" mode. The device also has a
built-in 1 MHz (nominal) oscillator for the PWM circuitry, or it can
be synchronized to an external 500 kHz to 1000 kHz clock signal.
Finally, it includes an integrated soft-start, cycle-by-cycle current
limiting, and thermal shutdown protection. The NCP1509 is
available in a space saving, low profile 3x3 mm 10 pin DFN package.
Features
High Efficiency:
92.5% for 1.8 V Output at 3.6 V Input and 125 mA Load Current
91% for 1.8 V Output at 3.6 V Input and 300 mA Load Current
Digital Programmable Output Voltages: 1.05, 1.35, 1.57 or 1.8 V
Output Current up to 500 mA at V
in
= 3.6 V
Low Quiescent Current of 14
mA in Pulsed Switching Mode
Low 0.2
mA Shutdown Current
-30C to 85C Operation Temperature
Low Profile DFN Package
Pb-Free Package is Available
Application
Cellular Phones, Smart Phones and PDAs
Digital Still Cameras
MP3 Players and Portable Audio Systems
Wireless and DSL Modems
Portable Equipment
MARKING
DIAGRAM
1509 = Specific Device Code
A
= Assembly Location
L
= Wafer Lot
Y
= Year
W
= Work Week
Device
Package
Shipping
ORDERING INFORMATION
10 Pin DFN
NCP1509MNR2
10 Pin DFN
(Pb-Free)
3000 Tape & Reel
NCP1509MNR2G
3000 Tape & Reel
For information on tape and reel specifications,
including part orientation and tape sizes, please
refer to our Tape and Reel Packaging Specifications
Brochure, BRD8011/D.
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10 PIN DFN
MN SUFFIX
CASE 485C
1509
ALYW
1
1
Figure 1. Typical Application Circuit
VCC
A
VCCP
SHD
SYNC
GNDA GNDP
CB0
CB1
FB
LX
V
in
2.
5 V - 5.2 V
6.8
uH
V
out
CB0 and CB1
Control Input
C
in
10
uF
C
out
22
uF
10
9
4
5
7
8
6
3
0
10
20
30
40
50
60
70
80
90
100
0.001
0.1
1
10
100
1000
I
out
(mA)
EFFICIENCY (%)
Figure 2. Efficiency vs. Output Current
Pulsed Mode
V
in
= 3.6 V
V
out
= 1.8 V
0.01
PWM Mode
1
2
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2
Figure 3. Simplified Block Diagram
+
-
-
+
+
-
+
-
+
-
+
-
FB
GNDA
CB0
CB1
SHD
ISENS
ISENS
SENFET
ILIM
ZCL
MODE SELECTION
SYNC DETECT
AND
TIMING BLOCK
SYNC DETECT
AND
TIMING BLOCK
THERMAL
SHUTDOWN
ENABLE
DETECT
SELECT
LOGIC
BANDGAP
REFERENCE
AND SOFT
START
PWM
OVP
PM
CMP
CMP
CMP
CMP
CMP
OA
Q2
Q1
DVR
DVR
COMPENSATION
RAMP
CONTROL
BLOCK
(PWM,PM)
GNDP
SYNC
LX
VCCA
VCCP
FB
DAMPING
SWITCHING
CONTROL
DAMPING
SWITCHING
CONTROL
2
10
6
3
4
5
6
1
7
8
9
PIN FUNCTION DESCRIPTION
Pin
Number
Name
Type
Description
1
GNDA
Analog GND
Ground connection for the Analog Section of the IC. This is the GND for the FB, SYNC,
CB0, CB1, PG and ENABLE pins.
2
GNDP
Power GND
Ground connection for the N-FET Power Stage.
3
LX
Power Output
Connection from Power MOSFETs to the Inductor.
4
VCCP
Power Input
Power Supply Input for the Switching P-FET.
5
VCCA
Power Input
Power Supply Input for the Analog Section of the IC.
6
FB
Analog Input
Feedback voltage from the output of the power supply.
7
CB0
Analog Input
V
out
Selection Pin. This pin contains a pulldown resistor.
8
CB1
Analog Input
V
out
Selection Pin. This pin contains a pullup resistor.
9
SHD
Analog Input
Enable for Switching Regulator. This pin is active high to turn on the NCP1509. This pin
contains an internal pulldown resistor.
10
SYNC
Analog Input
Synchronization input for the PWM converter. If a clock signal is present, the converter
uses the rising edge for the turn on of the PFET. If this pin is low, the converter is in Low Iq
Pulse mode. If this pin is high, the converter uses the internal oscillator for the PWM mode.
This pin has an internal pulldown resistor to force the operation into the Pulse mode.
NCP1509
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MAXIMUM RATINGS
Rating
Symbol
Value
Unit
Maximum Voltage All Pins
V
max
5.5
V
Maximum Operating Voltage All Pins
V
max
5.2
V
Thermal Resistance, Junction-to-Air
R
qJA
68.5
C/W
Operating Ambient Temperature Range
T
A
-30 to 85
C
ESD Withstand Voltage
Human Body Model (Note 1)
Machine Model (Note 1)
V
ESD
> 2500
> 150
V
Moisture Sensitivity
MSL
Level 1
Storage Temperature Range
T
stg
-55 to 150
C
Junction Operating Temperature
T
J
-30 to 125
C
Maximum ratings are those values beyond which device damage can occur. Maximum ratings applied to the device are individual stress limit values
(not normal operating conditions) and are not valid simultaneously. If these limits are exceeded, device functional operation is not implied, damage
may occur and reliability may be affected.
1. This device series contains ESD protection and exceeds the following tests:
Human Body Model, 100 pF discharge through a 1.5 k
W following specification JESD22/A114.
Machine Model, 200 pF discharged through all pins following specification JESD22/A115.
Latchup as per JESD78 Class II: > 100 mA.
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ELECTRICAL CHARACTERISTICS
(V
in
= 3.6 V, Vo = 1.57 V, T
A
= 25C, Fsyn = 600 kHz 50% Duty Cycle square wave for PWM
mode; T
A
= 30 to 85C for Min/Max values, unless otherwise noted.
Characteristic
Symbol
Min
Typ
Max
Unit
V
CC
Pin
Quiescent Current of SYNC Mode, I
out
= 0 mA
Iq PWM
-
175
-
mA
Quiescent Current of PWM Mode, I
out
= 0 mA
Iq PWM
-
185
-
mA
Quiescent Current of Pulsed Mode, I
out
= 0 mA
Iq Pulsed
-
14
-
mA
Quiescent Current, SHD Low
Iq Off
-
0.1
1.0
mA
Input Voltage Range
V
in
2.5
-
5.2
V
SYNC Pin
Input Voltage
Vsync
-0.3
-
Vcc + 0.3
V
Frequency Operational Range
Fsync
500
600
1000
kHz
Minimum Synchronization Pulse Width
Dcsync Min
-
5.0
-
%
Maximum Synchronization Pulse Width
Dcsync Max
-
95
-
%
SYNC "H" Voltage Threshold
Vsynch
-
920
1200
mV
SYNC "L" Voltage Threshold
Vsyncl
400
830
-
mV
SYNC "H" Input Current, Vsync = 3.6 V
Isynch
-
2.2
-
mA
SYNC "L" Input Current, Vsync = 0 V
Isyncl
-0.5
-
-
mA
Output Level Selection Pins
Input Voltage
Vcb
-0.3
-
Vcc + 0.3
V
CB0, CB1 "H" Voltage Threshold
Vcb h
-
920
1200
mV
CB0, CB1 "L" Voltage Threshold
Vcb l
400
830
-
mV
CB0 "H" Input Current, CB = 3.6 V
Icb0 h
-
2.2
-
mA
CB0 "L" Input Current, CB = 0 V
Icb0 l
-0.5
-
-
mA
CB1 "H" Input Current, CB = 3.6 V
Icb1 h
-
0.3
1.0
mA
CB1 "L" Input Current, CB = 0 V
Icb1 l
-
-2.2
-
mA
Shutdown Pin
Input Voltage
Vshd
-0.3
-
Vcc + 0.3
V
SHD "H" Voltage Threshold
Vshd h
-
920
1200
mV
SHD "L" Voltage Threshold
Vshd l
400
830
-
mV
SHD "H" Input Current, SHD = 3.6 V
Ishd h
-
2.2
-
mA
SHD "L" Input Current, SHD = 0 V
Ishd l
-0.5
-
-
mA
Feedback Pin
Input Voltage
Vfb
-0.3
-
Vcc + 0.3
V
Input Current, Vfb = 1.5 V
Ifb
-
5.0
7.5
mA
SYNC PWM Mode Characteristics
Switching P-FET Current Limit
I
lim
-
800
-
mA
Duty Cycle (Note 2)
DC
-
-
100
%
Minimum On Time
T
on(min)
-
75
-
nsec
R
DS(on)
Switching P-FET and N-FET
R
DS(on)
-
0.23
-
W
Switching P-FET and N-FET Leakage Current
I
leak
-
0
10
mA
Output Overvoltage Threshold
Vo
-
3.0
-
%
Feedback Voltage Accuracy, V
out
Set = 1.05 V
C
B0
= L, C
B1
= L, I
out
= 300 mA
V
out
1.018
1.050
1.082
V
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ELECTRICAL CHARACTERISTICS
(V
in
= 3.6 V, Vo = 1.57 V, T
A
= 25C, Fsyn = 600 kHz 50% Duty Cycle square wave for PWM
mode; T
A
= 30 to 85C for Min/Max values, unless otherwise noted.
Characteristic
Unit
Max
Typ
Min
Symbol
SYNC PWM Mode Characteristics (continued)
Feedback Voltage Accuracy, V
out
Set = 1.35 V, C
B0
= L, C
B1
= H,
I
out
= 300 mA
V
out
1.309
1.350
1.391
V
Feedback Voltage Accuracy, V
out
Set = 1.57 V, C
B0
= H, C
B1
= H,
I
out
= 300 mA
V
out
1.523
1.570
1.617
V
Feedback Voltage Accuracy, V
out
Set = 1.8 V, C
B0
= H, C
B1
= L,
I
out
= 300 mA
V
out
1.746
1.800
1.854
V
Line Regulation, V
in
= 2.7 V-3.6 V, I
out
= 100 mA
-
-15
-
+15
mV
Line Regulation, V
in
= 3.6 V-5.2 V, I
out
= 100 mA
-
-15
-
+15
mV
Load Regulation, I
out
= 100 mA-300 mA
-
-15
-
+15
mV
Load Transient Response, 10 to 100 mA Load Step
V
out
-
50
-
mV
Line Transient Response, I
out
= 100 mA, 3.0 to 3.6 V
in
Line Step
V
out
-
"5.0
-
mVpp
PWM Mode with Internal Oscillator Characteristics
Switching P-FET Current Limit
I
lim
-
800
-
mA
Duty Cycle (Note 2)
DC
-
-
100
%
Minimum On Time
T
on(min)
-
75
-
nsec
Internal Oscillator Frequency - T
A
= 25C
30C T
A
85C
Fosc
760
700
980
980
1240
1240
kHz
R
DS(on)
Switching P-FET and N_FET
R
DS(on)
-
0.23
-
W
Switching P-FET and N-FET Leakage Current
I
leak
-
0
10
mA
Output Overvoltage Threshold
Vo
-
3.0
-
%
Feedback Voltage Accuracy, V
out
Set = 1.05 V, C
B0
= L, C
B1
= L,
I
out
= 300 mA
V
out
1.018
1.050
1.082
V
Feedback Voltage Accuracy, V
out
Set = 1.35 V, C
B0
= L, C
B1
= H,
I
out
= 300 mA
V
out
1.309
1.350
1.391
V
Feedback Voltage Accuracy, V
out
Set = 1.57 V, C
B0
= H, C
B1
= H,
I
out
= 300 mA
V
out
1.523
1.570
1.617
V
Feedback Voltage Accuracy, V
out
Set = 1.8 V, C
B0
= H, C
B1
= L,
I
out
= 300 mA
V
out
1.746
1.800
1.854
V
Line Regulation, V
in
= 2.7 V-3.6 V, I
out
= 100 mA
-
-15
-
+15
mV
Line Regulation, V
in
= 3.6 V-5.2 V, I
out
= 100 mA
-
-15
-
+15
mV
Load Regulation, I
out
= 100 mA-300 mA
-
-15
-
+15
mV
Load Transient Response, 10 to 100 mA Load Step
V
out
-
50
-
mV
Line Transient Response, I
out
= 100 mA, 3.0 to 3.6 Vin Line Step
V
out
-
"5.0
-
mVpp
Pulsed Mode Characteristics
Peak Current Limit
I
lim
-
200
-
mA
Output Current
I
out
0.05
-
30
mA
Output Ripple Voltage, I
out
= 100
mA
V
out
-
22
100
mV
Feedback Voltage Accuracy, V
out
Set = 1.05 V, C
B0
= L, C
B1
= L
V
out
1.018
1.050
1.082
V
Feedback Voltage Accuracy, V
out
Set = 1.35 V, C
B0
= L, C
B1
= H
V
out
1.309
1.350
1.391
V
Feedback Voltage Accuracy, V
out
Set = 1.57 V, C
B0
= H, C
B1
= H
V
out
1.523
1.570
1.617
V
Feedback Voltage Accuracy, V
out
Set = 1.8 V, C
B0
= H, C
B1
= L
V
out
1.746
1.800
1.854
V
2. Maximum value is guaranteed by design.
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Figure 4. Efficiency vs. Output Current in
PWM Mode
V
in
(V)
EFFICIENCY (%)
70
75
80
85
90
95
100
2.7
3.2
3.7
4.2
4.7
5.2
1.05 V
out
1.35 V
out
1.57 V
out
1.8 V
out
I
out
= 100 mA PWM
T
A
= 25C
I
out
(mA)
EFFICIENCY (%)
0
100
200
300
400
500
1.8 V
out
1.57 V
out
1.35 V
out
1.05 V
out
V
in
= 3.6 V PWM
T
A
= 25C
Figure 5. Efficiency vs. Input Voltage in
PWM Mode
Figure 6. Efficiency vs. Output Current at
Different Input Voltage
Figure 7. Efficiency vs. Frequency
Figure 8. Efficiency vs. Frequency
Figure 9. Efficiency vs. Output Current in
Pulsed Mode
FREQUENCY (kHz)
EFFICIENCY (%)
500
700
900
1100
1300
1500
1.05 V
out
1.35 V
out
1.8 V
out
1.57 V
out
V
in
= 3.6 V
I
out
= 150 mA PWM
T
A
= 25C
80
84
82
86
88
90
94
0
10
20
30
40
50
60
70
80
90
100
0.01
0.1
1
10
100
0.001
I
out
(mA)
EFFICIENCY (%)
V
in
= 3.6 V PM
T
A
= 25C
0
10
20
30
40
50
60
70
80
90
100
I
out
(mA)
EFFICIENCY (%)
0
100
200
300
400
500
3.6 V
in
2.7 V
in
V
out
= 1.8 V PWM
T
A
= 25C
0
20
40
60
80
100
5.2 V
in
92
FREQUENCY (kHz)
EFFICIENCY (%)
500
700
900
1100
1300
1500
1.05 V
out
1.35 V
out
1.8 V
out
1.57 V
out
V
in
= 3.6 V
I
out
= 300 mA PWM
T
A
= 25C
80
84
82
86
88
90
94
92
1.05 V
out
1.35 V
out
1.57 V
out
1.8 V
out
10
30
50
70
90
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Figure 10. Input Current Comparison
Figure 11. Output Voltage vs. Output Current
Figure 12. Load Regulation in PWM Mode
60
40
20
0
-20
-40
TEMPERATURE (C)
FREQUENCY (kHz)
1100
1050
1000
950
900
850
V
in
= 3.6 V
V
out
= 1.8 V
I
out
= 100 mA
PWM
V
in
(V)
Figure 13. Output Voltage vs. Temperature
Figure 14. Oscillator Frequency vs. Temperature
Figure 15. Oscillator Frequency vs. Input
Voltage
0
4
8
12
16
0
5
10
15
20
30
I
out
(mA)
I
in
(mA)
PWM
Pulsed Mode
0.6
0.8
1.2
2.0
0
100
200
500
I
out
(mA)
V
out
(V)
1.6
1.0
1.4
1.8
300
1.57 V
out
1.35 V
out
1.05 V
out
1.8 V
out
V
in
= 3.6 V PWM
T
A
= 25C
20
-10
0
20
0
100
200
500
I
out
(mA)
DEL
T
A
V
out
(mV)
40
10
30
300
1.57 V
out
1.35 V
out
1.05 V
out
1.8 V
out
-40
-30
-20
V
in
= 3.6 V PWM
T
A
= 25C
0.5
0.8
2.0
-40
-20
0
100
TEMPERATURE (C)
V
out
(V)
1.1
1.4
20
1.57 V
out
1.35 V
out
1.05 V
out
1.8 V
out
V
in
= 3.6 V
I
out
= 100 mA PWM
25
V
in
= 3.6 V
V
out
= 1.5 V
T
A
= 25C
400
400
1.7
40
60
80
100
80
5.2
4.7
4.2
3.7
3.2
2.7
FREQUENCY (kHz)
1100
1050
1000
950
900
850
V
out
= 1.8 V
I
out
= 100 mA
PWM
T
A
= 25C
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Figure 16. Output Voltage vs. Shutdown Pin
Voltage
1.4
0.6
0.4
0.2
0
V
SHD
(V)
V
out
(V)
1.5
0
1.2
1.0
0.8
Figure 17. Transition Level of CB Pins
1.4
0.6
0.4
0.2
0
V
CB
(V)
V
out
(V)
1.5
0
0.5
1
1.2
1.0
0.8
2
2
1
0.5
V
in
= 3.6 V
V
out
= 1.5 V
PWM
T
A
= 25C
V
in
= 3.6 V
V
out
= 1.5 V
PWM
T
A
= 25C
Figure 18. Light-Load PWM Switching Waveform
(V
in
= 3.6 V, V
out
= 1.8 V, I
out
= 30 mA)
Figure 19. Heavy-Load PWM Switching Waveform
(V
in
= 3.6 V, V
out
= 1.8 V, I
out
= 300 mA)
Figure 20. Pulsed Mode Switching Waveform
(V
in
= 3.6 V, V
out
= 1.8 V, I
out
= 30 mA)
Figure 21. Soft-Start
(V
in
= 3.6 V, V
out
= 1.8 V, I
out
= 150 mA)
1
ms/div
1
ms/div
1
ms/div
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Figure 22. Line Transient Response
Figure 23. Load Transient Response
Figure 24. Output Voltage Transition
from 1.57 V to 1.8 V
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DETAILED OPERATING DESCRIPTION
Overview
The NCP1509 is a monolithic micro-power high
frequency PWM step-down DC-DC converter specifically
optimized for applications requiring high efficiency and a
small PCB footprint such as portable battery powered
products. It integrates synchronous rectification to
improve efficiency as well as eliminate the external
Schottky diode. High switching frequency allows for a low
profile inductor and capacitors to be used. Four digital
selectable output voltages (1.05, 1.35, 1.57 and 1.8 V) can
be generated from the input supply that can range from
2.7-5.2 V. All loop compensation is integrated as well
further reducing the external component count as well.
The DC-DC converter has two operating modes (normal
PWM, pulsed switching), which are intended to allow for
optimum efficiency under either light (up to 30 mA) or
heavy loads. The user determines the operating mode by
controlling the SYNC input. In addition the SYNC input
can be used to synchronize the PWM to an external system
clock signal in the range of 500-1000 kHz.
PWM Operating Mode
The NCP1509 can be set to current mode PWM
operation by connecting SYNC pin to V
CC
. In this mode,
the output voltage is regulated by modulating on-time
pulse width of the main switch Q1 at a fixed frequency of
1 MHz. The switching of the PMOS Q1 is controlled by a
flip-flop driven by the internal oscillator and a comparator
that compares the error signal from an error amplifier with
the sum of the sensed current signal and compensation
ramp. At the beginning of each cycle, the main switch Q1
is turned ON by the rising edge of the internal oscillation
clock. The inductor current ramps up until the sum of the
current sense signal and compensation ramp becomes
higher than the error voltage amplifier. Once this has
occurred, the PWM comparator resets the flip-flop, Q1 is
turned OFF and the synchronous switch Q2 is turned ON.
Q2 replaces the external Schottky diode to reduce the
conduction loss and improve the efficiency. To avoid
overall power loss, a certain amount of dead time is
introduced to ensure Q1 is completely turned OFF before
Q2 is being turned ON.
In continuous conduction mode (CCM), Q1 is turned ON
after Q2 is completely turned OFF to start a new clock
cycle. In discontinuous conduction mode (DCM), the zero
crossing comparator (ZLC) will turn off Q2 when the
inductor current drops to zero.
Overvoltage Protection
The overvoltage protection circuit is present in PWM
mode to prevent the output voltage from going too high
under light load or fast load transient conditions. The
output overvoltage threshold is 5% above nominal set
value. If the output voltage rises above 5% of the nominal
value, the OVP comparator is activated and switch Q1 is
turned OFF. Switching will continue when the output
voltage falls below the threshold of OVP comparator.
Pulsed Mode (PM)
Under light load conditions (< 30 mA), NCP1509 can be
configured to enter a low current pulsed mode operation to
reduce power consumption. This is accomplished by
SYNC pin held LOW. The output regulation is
implemented by pulse frequency modulation. If the output
voltage drops below the threshold of PM comparator
(typically Vnom-2%), a new cycle will be initiated by the
PM comparator to turn on the switch Q1. Q1 remains ON
until 200 mA inductor peak current is reached. Then ILIM
comparator goes high to switch off Q1. After a short dead
time delay, switch rectifier Q2 is turn ON. The zero
crossing comparator will detect when the inductor current
drops to zero and send the signal to turn off Q2. The output
voltage continues to decrease through discharging the
output capacitor. When the output voltage falls below the
threshold of PM comparator again, a new cycle starts
immediately.
Cycle-by-Cycle Current Limit
From the block diagram (Figure 3), an ILIM comparator
is used to realize cycle-by-cycle current limit protection.
The comparator compares the LX pin voltages with the
reference voltage from the SENFET, which is biased by
constant current. If the inductor current reaches the limit,
ILIM comparator detects the LX voltage falling below the
reference voltage from SENFET and releases the signal to
turn off the switch Q1. The cycle-by-cycle current limit is
set at 800 mA in PWM and 200 mA in PM.
Frequency Synchronization and Operating Mode
Selection
The SYNC pin can also be used for frequency
synchronization by connecting it with an external clock
signal. It operates in PWM mode when synchronized to an
external clock. The switching cycle initiates by the rising
edge of the clock. The synchronization clock signals
between 0.4 V and 1.2 V from 500 kHz to 1000 kHz.
Gating on and off the clock, the SYNC pin can also be
used to select between PM and PWM modes. It allows
efficient dynamical power management by adjusting the
converter operation to the specific system requirement. Set
SYNC pin low to select PM mode at light load conditions
(up to 30 mA) and set SYNC pin high or connect with
external clock to select PWM mode at heavy load condition
to achieve optimum efficiency. Table 1 shows the mode
selection with three different SYNC pin states.
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Table 1. Operating Mode Selection
SYNC Pin State
Operating Mode
LOW
Pulsed Mode (PM)
HIGH
PWM, 1 MHz Switch Frequency
CLOCK
PWM, Frequency Synchronization
Output Voltage Selection
The output voltage is digitally programmed to one of
four voltage levels depending on the logic state of CB0 and
CB1. Therefore if the NCP1509's load, such as a digital
cellular phone's baseband processor, supports dynamic
power management, the device can lower or raise its core
voltage under software control. When combined with the
pulsed current mode function in low load situations, this
active voltage management further stretches the useful
operating life of the handset between charges. Figure 24
shows a typical transition between 1.57 to 1.8 volts.
The output voltage levels are listed in Table 2. The CB0
has a pull down resistor and the CB1 has a pullup resistor.
The default output voltage is 1.35 V when CB0 and CB1 are
floating.
Table 2. Truth Table for CB0 and CB1 with the
corresponding output voltage
CB0
CB1
Vout(V)
0
0
1.05
0
1
1.35
1
1
1.57
1
0
1.8
Soft-Start
The NCP1509 uses soft-start to limit the inrush current
when the device is initially powered up or enabled.
Soft-start is implemented by gradually increasing the
reference voltage until it reaches the full reference voltage.
During startup, a pulsed current source charges the internal
soft-start capacitor to provide gradually increasing
reference voltage for the PWM loop. When the voltage
across the capacitor ramps up to the nominal reference
voltage, the pulsed current source will be switched off and
the reference voltage will switch to the regular reference
voltage. From Figure 21, it show the soft-start time is about
1.5 ms.
Shutdown Mode
When the SHD pin has a voltage applied of less than
0.4 V, the NCP1509 will be disabled. In shutdown mode,
the internal reference, oscillator and most of the control
circuitries are turned off. Therefore, the typical current
consumption will be 0.1
mA (typical value).
Applying a voltage above 1.2 V to SHD pin will enable
the device for normal operation. The device will go through
soft-start to normal operation.
Thermal Shutdown
Internal Thermal Shutdown circuitry is provided to
protect the integrated circuit in the event that the maximum
junction temperature is exceeded. If the junction
temperature exceeds 160C, the device shuts down. In this
mode switch Q1 and Q2 and the control circuits are all
turned off. The device restarts in soft-start after the
temperature drops below 135
_C. This feature is provided
to prevent catastrophic failures from accidental device
overheating and it is not intended as a substitute for proper
heatsinking.
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APPLICATIONS INFORMATION
Component Selection
Input Capacitor Selection
In PWM operating mode, the input current is pulsating
with large switching noise. Using an input bypass capacitor
can reduce the peak current transients drawn from the input
supply source, thereby reducing switching noise
significantly. The capacitance needed for the input bypass
capacitor depends on the source impedance of the input
supply. The RMS capacitor current is calculated as:
IRMS [ IO D @ D
(eq. 1)
The maximum RMS current occurs at 50% duty cycle
with maximum output current, which is I
O,max
/2.
For NCP1509, a low profile ceramic capacitor of 10
mF
should be used for most of the cases. For effective bypass
results, the input capacitor should be placed as close as
possible to the V
CC
Pin.
Inductor Value Selection
Selecting the proper inductor value is based on the
desired ripple current. The relationship between the
inductance and the inductor ripple current is given by the
equation in below.
DiL +
Vout
Lfs
1
*
Vout
Vin
(eq. 2)
Large value inductors will have small ripple current and
low value inductor will have high ripple current. For
NCP1509, the compensation is internally fixed and a fixed
6.8
mH inductor is needed for most of the applications.
Output Capacitor Selection
Selecting the proper output capacitor is based on the
desired output ripple voltage. Ceramic capacitors with low
ESR values will have the lowest output ripple voltage and
are strongly recommended. The output ripple voltage is
given by:
DVc + DiL @ ESR )
1
4fsCout
(eq. 3)
The RMS output capacitor current is given by:
IRMS(Cout) +
VO @ (1 * D)
2 3
@ L @ fs
(eq. 4)
Where f
s
is the switching frequency and ESR is the
effective series resistance of the output capacitor. A low
ESR, 22
mF ceramic capacitor is recommended for
NCP1509 in most of applications. For example, with TDK
C2012X5R0J226 output capacitor, the output ripple is less
than 10 mV at 300 mA.
Design Example
As a design example, assume that the NCP1509 is used
in a single lithium-ion battery application. The input
voltage, V
in
, is 3.0 V to 4.2 V. Output condition is V
out
at
1.8 V with a typical load current of 120 mA and a maximum
of 300 mA. For NCP1509, the inductor has a predetermined
value, 6.8
mH. The inductor ESR will factor into the overall
efficiency of the converter. The inductor needs to be
selected by the required peak current.
Equation 5 is the basic equation for an inductor and
describes the voltage across the inductor. The inductance
value determines the slope of the current of the inductor.
VL
L
+
diL
dt
(eq. 5)
Equation 5 is rearranged to solve for the change in
current for the on-time of the converter in Continuous
Conduction Mode.
(eq. 6)
iL, pk-pk +
(Vin * Vout)
L
@ DTs
+
(Vin * Vout)
L
@
Vin
Vout
@
1
fs
iL, max + IO, max )
DiL, pk-pk
2
Utilizing Equations 6, the peak-to-peak inductor current
is calculated using the following worst-case conditions.
Vin, max + 4.2 V, Vout + 1.8 V, fs + 1 MHz-20%,
L
+ 6.8 mH-10%, iL, pk-pk + 211 mA, iL, max + 405 mA
Therefore, the inductor must have a maximum current
exceeding 405 mA.
Since the compensation is fixed internally in the IC, the
input and output capacitors as well as the inductor have a
predetermined value too: C
in
= 10
mF and C
out
= 22
mF. Low
ESR capacitors are needed for best performance.
Therefore, ceramic capacitors are recommended. Please
see Table 3 for recommended inductors and capacitors.
PCB Layout Recommendations
Good PCB layout plays an important role in switching
mode power conversion. Careful PCB layout can help to
minimize ground bounce, EMI noise and unwanted
feedbacks that can affect the performance of the converter.
Hints suggested below can be used as a guideline in most
situations.
1. Use star-ground connection to connect the IC ground
nodes and capacitor GND nodes together at one point.
Keep them as close as possible. And then connect this to the
ground plane (if it is used) through several vias. This will
reduce noise in ground plane by preventing the switching
currents from flowing through the ground plane.
2. Place the power components (i.e., input capacitor,
inductor and output capacitor) as close together as possible
for best performance. All connecting traces must be short,
direct, and thick to reduce voltage errors caused by
resistive losses across these traces.
3. Separate the feedback path of the output voltage from
the power path. Keep this path close to the NCP1509
circuit. And also route it away from noisy components.
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This will prevent noise from coupling into voltage
feedback trace.
4. Place the DC-DC converter away from noise sensitive
circuitry, such as RF circuits. Interference with noise
sensitive circuitry in the DC-DC converter can be reduced
by distance between them.
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