March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

GENERAL DESCRIPTION

The TEA1064A is a bipolar integrated circuit that performs
all the speech and line interface functions required in fully
electronic telephone sets. It performs electronic switching
between dialling and speech and has a powerful DC
supply for peripheral circuits. The IC operates at line
voltages down to 1.8 V DC (with reduced performance) to
facilitate the use of more telephone sets connected in
parallel. The transmit signal on the line is dynamically
limited (speech-controlled) to prevent distortion at high
transmit levels of both the sending signal and the sidetone.

FEATURES

Low DC line voltage; operates down to 1.8 V (excluding
polarity guard)

Voltage regulator with low voltage drop and adjustable
static resistance

DC line voltage adjustment facility

Provides a supply for external circuits in two options:

unregulated supply, regulated line voltage;

stabilized supply, line voltage varies with supply
current

Dynamic limiting (speech-controlled) in transmit
direction prevents distortion of line signal and sidetone

Symmetrical high-impedance inputs (64 k

) for

dynamic, magnetic or piezo-electric microphones

Asymmetrical high-impedance input (32 k

) for electret

microphones

DTMF signal input

Confidence tone in the earpiece during DTMF dialling

Mute input for disabling speech during pulse or DTMF
dialling

Power-down input for improved performance during
pulse dial or register recall (flash)

Receiving amplifier for magnetic, dynamic or
piezo-electric earpieces

Large amplification setting ranges on microphone and
earpiece amplifiers

Line loss compensation (line current dependent) for
microphone and earpiece amplifiers (not used for DTMF
amplifier)

Gain control curve adaptable to exchange supply

Automatic disabling of the DTMF amplifier in
extremely-low voltage conditions

Microphone MUTE function available with switch

PACKAGE OUTLINES

Notes

1. SOT146-1; 1998 Jun 18.

2. SOT163-1; 1998 Jun 18.

TEA1064A :20-lead DIL; plastic (SOT146).

(1)

TEA1064AT:20-lead mini-pack; plastic (SO20;
SOT163A).

(2)

March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

QUICK REFERENCE DATA

PARAMETER

CONDITIONS

SYMBOL

MIN.

TYP.

MAX.

UNIT

Operating ambient temperature

range

amb

Line current operating range:

normal operation

line

140

(1)

with reduced performance

line

Internal supply current:

power-down input LOW

CC1

= 2.8 V

CC1

1.3

1.6

power-down input HIGH

CC1

= 2.8 V

CC1

Voltage gain range:

microphone amplifier

receiving amplifier

Line loss compensation:

gain control range

5.7

6.1

6.5

exchange supply voltage

range

exch

exchange feeding bridge

resistance range

exch

400

1000

Maximum output voltage swing

on LN (peak-to-peak value)

R15

R16 = 448

line

= 15 mA

= 2 mA

LN(p-p)

3.7

3.95

4.2

= 4 mA

LN(p-p)

3.0

3.25

3.5

Regulated line voltage application

R15 = 0

;

R16 = 392

Supply for peripherals

line

= 15 mA

= 1.4 mA

2.5

= 2.7 mA;

REG-SLPE

= 20 k

2.9

DC line voltage

line

= 15 mA

without R

REG-SLPE

3.57

REG-SLPE

= 20 k

4.57

March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

Note

1. For TEA1064AT the maximum line current depends on the heat dissipating qualities of the mounted device.

Stabilized supply voltage application

R15 = 392

;

R16 = 56

Supply for peripherals

line

= 15 mA

= 0 to 4 mA

CC2-SLPE

3.05

3.3

3.55

DC line voltage

line

= 15 mA

= 2 mA

4.2

4.4

4.8

= 4 mA

4.9

5.1

5.5

PARAMETER

CONDITIONS

SYMBOL

MIN.

TYP.

MAX.

UNIT

PINNING

Fig.2 Pinning diagram.

handbook, halfpage

GAS1

GAS2

GAR

DLS/MMUTE

MIC

STAB

SLPE

VCC2

AGC

REG

MUTE

VCC1

DTMF

VEE

TEA1064A

MGR057

1 LN

positive line terminal

2 GAS1

gain adjustment; transmitting amplifier

3 GAS2

gain adjustment; transmitting amplifier

4 QR

inverting output, receiving amplifier

5 QR

non-inverting output, receiving
amplifier

6 GAR

gain adjustment; receiving amplifier

7 DLS/

MMUTE

decoupling for transmit amplifier
dynamic and microphone MUTE input

8 MIC

inverting microphone input

9 MIC

non-inverting microphone input

10 STAB

current stabilizer

11 V

negative line terminal

12 DTMF

dual-tone multi-frequency input

13 IR

receiving amplifier input

14 MUTE

mute input

15 PD

power-down input

16 V

CC1

internal supply decoupling

17 REG

voltage regulator decoupling

18 AGC

automatic gain control input

19 V

CC2

reference voltage with respect to SLPE

20 SLPE

slope adjustment for DC
curve/reference for peripheral circuits.

March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

FUNCTIONAL DESCRIPTION

Supplies V

CC1

, V

CC2

, LN, SLPE, REG and STAB (Fig.3)

Power for the TEA1064A and its peripheral circuits is
usually obtained from the telephone line. The IC develops
its own supply voltage at V

CC1

and regulates its voltage

drop. The internal supply requires a decoupling capacitor
between V

CC1

and V

. The internal current stabilizer is

set by a 3.6 k

resistor between STAB and V

The DC current flowing into the set is determined by the
exchange supply voltage V

exch

, the feeding bridge

resistance R

exch

, the subscriber line DC resistance R

line

and the DC voltage (including polarity guard) on the
subscriber set (see Fig.3).

The internal voltage regulator generates a
temperature-compensated reference voltage that is
available between V

CC2

and SLPE

ref

= V

CC2-SLPE

= 3.3 V (typ.)]. This internal voltage

regulator requires decoupling by a capacitor between REG
and V

(C3).

The reference voltage can be used to:

regulate directly the line voltage (stabilized
V

LN-SLPE

= V

CC2-SLPE

)

(1)

to stabilize the supply voltage for peripherals.

Regulated line voltage

In this application the V

CC2

pin is connected to the LN pin

as shown in Fig.3. This configuration gives a stabilized
voltage across pins LN and SLPE which, applied via the
low-pass filter R16, C15, provides a supply to the
peripherals that is independent of the line current and
depends only on the peripheral supply current.

The value of R16 and the level of the DC voltage V

LN-SLPE

determine the supply capabilities. In the basic application
R16 = 392

and C15 = 220

F. The worst-case

peripheral supply current as a function of supply voltage is
shown in Fig.4. To increase the supply capabilities, the DC
voltage V

LN-SLPE

can be increased by using R

VA(REG-SLPE)

or by decreasing the value of R16.

(1) The TEA1064A application with regulated line voltage is the

same as is used for TEA1060/TEA1061, TEA1067 and
TEA1068 integrated circuits.

Fig.3 Application with regulated line voltage (stabilized V

LN-SLPE

The voltage V

LN-SLPE

is fixed to V

ref

= 3.3

0.25 V. Resistor R16 together with the

line current determine the supply capabilities and the maximum output swing on
the line (no loop damping is necessary).
The line voltage V

= V

ref

([I

line

1.55 mA]

R9).

handbook, full pagewidth

MGR058

Rexch

Rline

Iline

Vexch

REG

STAB

SLPE

VCC1

19 VCC2

VEE

0.25 mA

ISLPE

ICC1

R16

C15

peripheral

circuits

TEA1064A

0.25 mA

March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

The maximum AC output swing on the line at low line
currents is influenced by R16 (limited by current) and the
maximum output swing on the line at high line currents is
influenced by the DC voltage V

LN-SLPE

(limited by voltage).

In both these situations, the internal dynamic limiter in the
sending channel prevents distortion when the microphone
input is overdriven. The maximum AC output swing on LN
is shown in Fig.5; practical values for R16 are from 200 to
600

and this influences both the maximum output swing

at low line currents and the supply capabilities.

The SLPE pin is the ground reference for peripheral
circuits, therefore inputs MUTE, PD and DTMF are also
referenced to SLPE.

Active microphones can be supplied between V

CC1

and

. Low-power circuits that provide only MUTE and/or PD

inputs to the TEA1064A also can be powered from V

CC1

However V

CC1

cannot be used for circuits that provide

DTMF signals to the TEA1064A because V

CC1

is referred

to ground.

If the line current l

line

exceeds I

CC1

0.25 mA, the voltage

converter shunts the excess current to SLPE via LN;
where I

CC1

1.3 mA, the value required by the IC for

normal operation.

Fig.4

Minimum supply current for peripherals (I

)

as a function of the peripheral supply
voltage (V

handbook, halfpage

MGR059

Vp (V)

(mA)

VA (REG-SLPE)

= 20 k

without

VA (REG-SLPE)

line

= 15 mA; R16 = 392

; R15 = 0

; valid for MUTE = 0 and 1.

Line current has very little influence

The DC line voltage on LN is:

= V

LN-SLPE

SLPE

R9)

= V

ref

([I

line

CC1

0.25

R9)

in which

ref

= 3.3 V

0.25 V is the internal reference voltage

between V

CC2

and SLPE; its value can be adjusted by

external resistor R

R9 = external resistor between SLPE and V

(20

basic application).

With R9 = 20

, this results in:

= 3.57

0.25 V at l

line

= 15 mA

= 4.17

0.3 V at l

line

= 15 mA,

VA(REG-SLPE)

= 33 k

= 4.57

0.35 V at l

line

= 15 mA,

VA(REG-SLPE)

= 20 k

The preferred value for R9 is 20

. Changing R9

influences microphone gain, DTMF gain, the gain control
characteristics, sidetone, and the DC characteristics
(especially the low voltage characteristics).

In normal conditions, I

SLPE

>> (I

CC1

0.25 mA) and the

static behaviour is equivalent to a voltage regulator diode
with an internal resistance of R9. In the audio frequency
range the dynamic impedance is determined mainly by R1.
The equivalent impedance of the circuit in the audio
frequency range is shown in Fig.6.

The internal reference voltage V

CC2-SLPE

can be increased

by external resistor R

VA(REG-SLPE)

connected between

REG and SLPE. The supply voltage V

CC2-SLPE

is shown as

a function of R

VA(REG-SLPE)

in Fig.7. Changing the

reference voltage influences the output swing of both
sending and receiving amplifiers.

At line currents below 8 mA (typ.), the DC voltage dropped
across the circuit is adjusted to a lower level automatically
(approximately 1.8 V at 2 mA). This gives the possibility of
operating more telephone sets in parallel with DC line
voltages (excluding polarity guard) down to an absolute
minimum of 1.8 V. At line currents below 8 mA (typ.), the
circuit has limited sending and receiving levels.

March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

Fig.5

Maximum AC output swing on the line as a
function of line current with peripheral
supply current as a parameter: R15 = 0

;

R16 = 392

handbook, halfpage

MGR060

Iline (mA)

VLN(p-p)

(V)

Ip =
0 mA
2 mA
4 mA

Fig.6

Equivalent impedance between LN and
V

in the application with stabilized

LN-SLPE

R15 = 0

= C3

= 15 k

handbook, halfpage

MGR061

R9
20

REG

C3
4.7

Vref

Leq

VCC1

VEE

Fig.7

Internal reference voltage V

CC2-SLPE

as a function of resistor R

VA(REG-SLPE)

for line currents between 11

and 140 mA.

In the stabilized supply application:

= V

CC2-SLPE

([I

0.25

R15)

([I

line

1.55

R9)

In the unregulated supply application (R15 = 0

= V

CC2-SLPE

([I

line

1.55

R9)

handbook, full pagewidth

7.8

3.0

120

MGR062

4.2

5.4

6.6

RVA (REG-SLPE) (k

)

Vref

(V)

with RVA
infinite

March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

Stabilized peripheral supply voltage

The configuration shown in Fig.8 provides a stabilized
voltage across pins V

CC2

and SLPE for peripheral circuits

(such as dialling and control circuits); the DC voltage
V

now varies with the peripheral supply current.

The V

CC2-SLPE

supply must be decoupled by capacitor

C15. For stable loop operation, resistor R16 (

) is

connected between V

CC2

and SLPE in series with C15.

The voltage regulator control loop is completed by resistor
R15 between LN and V

CC2

For sets with an impedance of 600

, practical values are:

R15 = 200 to 600

; C15 = 220

F; C3 = 470 nF. The

ratio R15/R16

8 is for stable loop operation with

sufficient phase margin, and R15/R16

6 is for

satisfactory set impedance in the audio frequency range.

For sets with complex impedance, the value of C3 and the
ratio R15/R16 are different (further information is given in
the TEA1064A Application Report

(1)

The peripheral supply capability depends mainly on the
available line current, the required AC output swing on the
line, the maximum permitted DC voltage on the line and

the values of external components (especially R15). With
R15 = 392

and R16 = 56

(basic application) the

maximum possible AC output swing on the line as a
function of line current is as shown in Fig.9, the curve
parameter is the peripheral supply current (I

). Different

values for R15 (from 200 to 600

) maintaining

R15/R16

8 give different results (these are described

in the TEA1064A Application Report

(1)

(1) Supplied on request.

Fig.8 Application with stabilized supply voltage for peripheral circuits: R15 = 392

; R16 = 56

handbook, full pagewidth

MGR063

Rexch

Rline

Iline

Vexch

REG

STAB

SLPE

VCC1

19 VCC2

VEE

0.25 mA

R15

ISLPE

ICC1

R16

C15

peripheral

circuits

TEA1064A

0.25 mA

March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

The DC line voltage on LN is

= V

LN-SLPE

SLPE

R9).

Therefore

= V

ref

([I

0.25

R15)

([l

line

CC1

0.25

R9)

in which:

ref

is the internal reference voltage between V

CC2

and

SLPE (the value of V

ref

can be adjusted by an external

resistor, R

). V

ref

= 3.3 V (typ.) without R

is the supply current used by peripheral circuits

R15 is an external resistor between LN and V

CC2

(392

in the basic application)

R9 is an external resistor between SLPE and
V

(20

in the basic application)

The DC voltage V

LN-SLPE

as a function of I

with R15 as a

parameter is shown in Fig.10. In the audio frequency
range, the dynamic impedance is determined mainly by
R1. The equivalent impedance in the audio range of the
circuit (Fig.8) is shown in Fig.11.

Fig.9

Maximum output swing on line as a function
of line current with the peripheral supply
current as a parameter; R15 = 392

;

R16 = 56

As different values of R15 and R16 are allowed, different curves
would then apply

handbook, halfpage

MGR064

Iline (mA)

VLN(p-p)

(V)

Ip = 4 mA

2 mA

0 mA

Fig.10 Curves showing the typical voltage drop

between LN and SLPE as a function of the
supply current for peripherals with R15 as a
parameter: V

CC2-SLPE

= 3.3 V (R

not

connected).

CC2-SLPE

can be adjusted between approximately 3.3 and 4.3 V by

changing the value of R

, this results in a parallel-shift of the curves.

The total voltage drop V

LN-SLPE

([I

line

1.55 mA]

R9).

handbook, halfpage

5.5

3.0

5.0

MGR065

4.0

4.5

3.5

Ip (mA)

VLN-SLPE

(V)

R15 = 511

392

301

Fig.11 Equivalent impedance between LN and

at f

300 Hz in the application with

stabilized supply voltage for peripheral
circuits.

R15
R16

-----------

with R

15 k

handbook, halfpage

MGR066

R9
20

C3
470 nF

Req

Leq

VEE

R1
620

March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

Microphone inputs MIC

and MIC

and gain pins

GAS1 and GAS2

The TEA1064A has symmetrical microphone inputs, its
input impedance is 64 k

32 k

) and its voltage

amplification is typ. 52 dB with R7 = 68 k

. Either

dynamic, magnetic or piezo-electric microphones can be
used, or an electret microphone with a built-in FET buffer.
Arrangements for the microphone types are shown in
Fig.12.

The gain of the microphone amplifier is proportional to
external resistor R7 connected between GAS1 and GAS2
and with this it can be adjusted between 44 dB and 52 dB
to suit the sensitivity of the transducer.

An external 100 pF capacitor (C6) is required between
GAS1 and SLPE to ensure stability. A larger value of C6
may be chosen to obtain a first-order low-pass filter with a
cut-off frequency corresponding to the time constant
R7

C6.

Fig.12 Microphone arrangements: a) magnetic or dynamic microphone, the resistor (1) may be connected to

reduce the terminating impedance, or for sensitive types a resistive attenuator can be used to prevent
overloading the microphone inputs; b) electret microphone; c) piezo-electric microphone.

handbook, full pagewidth

MGR067

VEE

VCC1

(1)

(a)

(b)

(c)

MIC

Dynamic limiter (microphone) pin DLS/MMUTE

A low level at the DLS/MMUTE pin inhibits the microphone
inputs MIC

and MIC

but has no influence on the

receiving and DTMF amplifiers.
Removing the low level at the DLS/MMUTE pin provides
the normal function of the microphone amplifier after a
short time determined by the capacitor connected to
DLS/MMUTE pin. The microphone mute function can be
realised by a simple switch as shown in Fig.13.

To prevent distortion of the transmitted signal, the gain of
the sending amplifier is reduced rapidly when peaks of the
signal on the line exceed an internally-determined
threshold. The time in which gain reduction is effected
(attack time) is very short. The circuit stays in the
gain-reduced condition until the peaks of the sending
signal remain below the threshold level. The sending gain
then returns to normal after a time determined by the
capacitor connected to DLS/MMUTE (release time).

The internal threshold adapts automatically to the DC
voltage setting of the circuit (voltage V

LN-SLPE

). This

means that the maximum output swing on the line will be
higher if the DC voltage dropped across the circuit is
increased.

Fig.14 shows the maximum possible output swing on the
line as a function of the DC voltage drop (V

LN-SLPE

) with

line

as a parameter.

Fig.13 Microphone-mute function.

handbook, halfpage

MGR068

R17
3.3 k

DLS/MMUTE

VEE

March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

Fig.14 Maximum output swing on line as a function of the DC voltage drop V

LN-SLPE

with l

line

as a parameter:

R15 = 392

; R16 = 56

; or R15 = 0

and R16 = 392

56 = 448

handbook, full pagewidth

5.5

3.5

4.5

VLN(p-p)

(V)

VLN-VSLPE (V)

Iline-Ip

(mA)

MGR069

The internal threshold level is lowered automatically if the
DC current in the transmit output stage is insufficient. This
prevents distortion of the sending signal in applications
using parallel-connected telephones or telephones
operating over long lines, for example.

Dynamic limiting also considerably improves sidetone
performance in over-drive conditions (less distortion;
limited sidetone level).

Receiving amplifier IR, QR

, QR

and GAR

The receiving amplifier has one input IR and two
complementary outputs, QR

(non-inverting) and QR

(inverting). These outputs may be used for single-ended or
differential drive, depending on the type and sensitivity of
the earpiece used (see Fig.15). Gain from IR to QR

typically 31 dB with R4 = 100 k

, sufficient for

low-impedance magnetic or dynamic earpieces which are
suitable for single-ended drive. By using both outputs
(differential drive) the gain is increased by 6 dB.
Differential drive can be used when the earpiece
impedance exceeds 450

as with high-impedance

dynamic, magnetic or piezo-electric earpieces.

Fig.15 Alternative receiver arrangements: a) dynamic earpiece with an impedance less than 450

; b) dynamic

earpiece with an impedance more than 450

; c) magnetic earpiece with an impedance more than 450

resistor (1) may be connected to prevent distortion (inductive load); d) piezo-electric earpiece, resistor (2)
is required to increase the phase margin (stability with capacitive load).

handbook, full pagewidth

MGR070

(1)

VEE

(2)

(a)

(b)

(c)

(d)

March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

The output voltage of the receiving amplifier is specified for
continuous-wave drive. Fig.16 shows the maximum output
swing of the receiving amplifier as a function of the DC
voltage drop (V

). The maximum output voltage will be

higher under speech conditions, where the ratio of the
peak to the RMS value is higher.

The gain of the receiving amplifier can be adjusted to suit
the sensitivity of the transducer used. The adjustment
range is between 20 dB and 39 dB with single-ended drive
and between 26 dB and 45 dB with differential drive. The
gain is proportional to the external resistor R4 connected
between GAR and QR

. The overall gain between LN and

can be found by subtracting the attenuation of the

anti-sidetone network (32 dB) from the amplifier gain.

Two external capacitors (C4 =100 pF and
C7 = 10

C4 = 1 nF) ensure stability. A larger value may

be chosen to obtain a first-order low-pass filter. The cut-off
frequency corresponds with the time constant R4

C4.

The relationship C7 = 10

C4 must be maintained.

Fig.16 Maximum output swing of the receiving amplifier as a function of DC voltage drop V

with the load at the

receiver output as parameter: valid for both supply options; THD = 2%; I

line

= 15 mA.

Curve (1) is for a differential load of 47 nF (series
resistance = 100

); f = 3400 Hz.

Curve (2) is for a differential load of 450

; f = 1 kHz.

Curve (3) is for a single-ended load of 150

; f = 1 kHz.

handbook, halfpage

1.5

0.5

1.0

MGR071

VLN (V)

VQR(rms)

(V)

(2)

(3)

(1)

Automatic gain control input AGC

Automatic compensation of line loss is obtained by
connecting a resistor (R6) between AGC and V

. This

automatic gain control varies the gain of the microphone
amplifier and receiving amplifier in accordance with the DC
line current. The control range is 6.1 dB; this corresponds
to a 5 km line of 0.5 mm diameter copper twisted-pair
cable (DC resistance = 176

/km, average

attenuation = 1.2 dB/km). The DTMF gain is not affected
by this feature.

The value of R6 must be chosen with reference to the
exchange supply voltage and its feeding bridge resistance
(see Fig.17 and Table 1). Different values of R6 give the
same line current ratios at the start and the end of the
control range. If automatic line-loss compensation is not
required the AGC pin can be left open, the amplifiers then
give their maximum gain.

March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

Fig.17 Variation of gain as a function of line current with R6 as a parameter; R9 = 20

handbook, full pagewidth

MGR072

Avd

(dB)

Iline (mA)

93.1 k

66.5 k

R6 =

118 k

Table 1

Values of R6 giving optimum line-loss
compensation at various values of exchange
supply voltage (V

exch

) and exchange feeding

bridge resistance (R

exch

); R9 = 20

MUTE input (see notes 1. and 2.)

MUTE = HIGH enables the DTMF input and inhibits the
microphone and receiving amplifier inputs.

MUTE = LOW or open-circuit disables the DTMF input and
enables the microphone and receiving amplifier inputs.

Switching MUTE gives negligible clicks at the telephone
outputs and on the line.

Dual-tone multi-frequency input DTMF (see note 1.)

When the DTMF input is enabled, dialling tones may be
sent on to the line. The voltage gain between DTMF-SLPE
and LN-V

is typ. 26 dB less than the gain of the

microphone amplifier and varies with R7 in the same way
as the gain of the microphone amplifier. This means that
the tone level at the DTMF input has to be adjusted after

exch

(

)

400

600

800

1000

R6 (k

)

exch

(V)

84.5

66.5

118

93.1

77.8

66.5

97.6

84.5

setting the gain of the microphone amplifier. With
R7 = 68 k

the gain is typically 26 dB.

The signalling tones can be heard in the earpiece at a low
level (confidence tone).

Power-down input PD (see notes 1. and 2.)

During pulse dialling or register recall (timed loop break)
the telephone line is interrupted; as a consequence it
provides no supply for the transmission circuit connected
to V

CC1

or for the peripherals between V

CC2

and SLPE.

These supply gaps are bridged by the charges in the
capacitors C1 and C15. The requirements on these
capacitors are eased by applying a HIGH level to the PD
input during the time of the loop break. This reduces the
internal supply current I

CC1

from (typ.) 1.3 mA to (typ.)

A and switches off the voltage regulator to prevent

discharge via LN and V

CC2

A HIGH level at PD also internally disconnects the
capacitor at REG so that the voltage stabilizer has no
switch-on delay after line interruptions. This minimizes the
contribution of the IC to the current waveform during pulse
dialling or register recall.

When the power-down facility is not required, the PD pin
can be left open-circuit or connected to SLPE.

Side-tone suppression

Suppression of the transmitted signal in the earpiece is
obtained by the anti-sidetone network comprising R1//Z

line

March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

R2, R3, R8, R9 and Z

bal

(see Fig.18). Maximum

compensation is obtained when the following conditions
are fulfilled:

a) R9

R2 = R1

(R3

[R8//Z

bal

])

b) (Z

bal

/[Z

bal

R8]) = (Z

line

/[Z

line

R1])

If fixed values are chosen for R1, R2, R3 and R9, then
condition a) is always fulfilled provided

R8//Z

bal

<< R3.

To obtain optimum sidetone suppression, condition b) has
to be fulfilled, resulting in:

bal

= (R8/R1)

line

= k

line

where k is a scale factor; k = (R8/R1).

The scale factor k (value of R8) is chosen to meet the
following criteria:

compatibility with a standard capacitor from the E6 or
E12 range for Z

bal

;

bal

//R8

<< R3 to fulfil condition a) and thus ensure

correct anti-sidetone bridge operation;

bal

>> R9 to avoid influencing the transmit gain.

In practice Z

line

varies considerably with the line length and

line type. Therefore the value chosen for Z

bal

should be for

an average line length giving satisfactory sidetone
suppression with short and long lines. The suppression
also depends on the accuracy of the match between
Z

bal

and the impedance of the average line.

Example

The line impedance for which optimum suppression is to
be obtained can be represented by
210

(1265

// 140 nF). This represents a 5 km line of

0.5 mm diameter copper twisted-pair cable matched with
600

(176

/km; 38 nF/km).

With k = 0.64 this results in: R8 = 390

;

bal

= 130

(820

// 220 nF).

The anti-sidetone network for the TEA1060 family shown
in Fig.18 attenuates the signal received from the line by
32 dB before it enters the receiving amplifier. The
attenuation is almost constant over the whole
audio-frequency range.

Alternatively a conventional Wheatstone bridge can be
used as an anti-sidetone circuit (Fig.19). Both bridge types
can be used with either resistive or complex set
impedances. (More information on the balancing of
anti-sidetone bridges can be obtained in our publication
"Versatile speech transmission ICs for electronic
telephone sets", order number 9398 341 10011).

Notes
1. The reference used for the MUTE, DTMF and PD

inputs is SLPE.

2. A LOW level for any of these pins is defined by

connection to SLPE, a HIGH level is defined as a
voltage greater than V

SLPE

1.5 V and smaller than

CC1

0.4 V.

March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

RATINGS

Limiting values in accordance with the Absolute Maximum System (IEC 134)

Notes

1. Mostly dependent on the maximum required T

amb

and on the voltage between LN and SLPE. See Figs 20 and 21 to

determine the current as a function of the required voltage and the temperature.

2. Calculated for the maximum ambient temperature specified T

amb

= 75

C and a maximum junction temperature of

125

THERMAL RESISTANCE

PARAMETER

CONDITIONS

SYMBOL

MIN.

MAX.

UNIT

Positive line voltage continuous

Repetitive line voltage during

switch-on line interruption

13.2

Repetitive peak line voltage

one 1 ms pulse per 5 s

R9 = 20

;

R10 = 13

(Fig.24)

Line current TEA1064A (note 1)

R9 = 20

140

Line current TEA1064AT (note 1)

R9 = 20

140

Input voltage on pins other than

LN and V

CC2

0.7

CC1

0.7

Total power dissipation (note 2)

R9 = 20

TEA1064A

tot

714

TEA1064AT

tot

555

Storage temperature range

stg

125

Operating ambient temperature range

amb

Junction temperature

125

From junction to ambient in free air

TEA1064A

th j-a

70 K/W

TEA1064AT mounted on glass epoxy board 41

1.5 mm

th j-a

90 K/W

March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

CHARACTERISTICS

line

= 11 to 140 mA; V

= 0 V; f = 800 Hz; T

amb

= 25

C; R

= 600

; tested in the circuit of Fig.22 or 23); unless

otherwise specified

PARAMETER

CONDITIONS

SYMBOL

MIN.

TYP.

MAX.

UNIT

Supplies LN, V

CC1

, V

CC2

(pins 1, 16, 19)

Reference DC voltage between

CC2

and SLPE

line

= 15 mA

= 0; 4 mA

not connected

CC2-SLPE

3.05

3.3

3.55

Variation with temperature

line

= 15 mA

CC2-SLPE

3.0

1.0

mV/K

Variation with line current referred

to 15 mA

line

= 100 mA

CC2-SLPE

With R

connected between

REG and SLPE

= 33 k

CC2-SLPE

3.6

3.8

4.2

= 20 k

CC2-SLPE

3.95

4.2

4.65

DC line voltage:

voltage drop between LN and V

MIC

, MIC

inputs open;

R15 = 392

;

without R

at I

line

= 15 mA

= 0 mA

3.4

3.6

4.0

= 2 mA

4.2

4.4

4.8

= 4 mA

4.9

5.1

5.5

at I

line

= 100 mA

= 2 mA

6.1

7.0

at I

line

= 140 mA

Ip = 2 mA

7.0

7.8

Voltage drop under low current

conditions

= 0 mA

line

= 2 mA

1.8

line

= 4 mA

2.2

line

= 7 mA

3.2

line

= 11 mA

3.5

Internal supply current I

CC1

current into pin V

CC1

= 2.8 V

PD = LOW

CC1

1.3

1.6

PD = HIGH

CC1

Microphone inputs MIC

, MIC

(pins 8, 9)

Input impedance:

differential

single-ended

25.5

32.0

38.5

Common mode rejection ratio

CMRR

March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

Voltage gain (see Fig.22)

line

= 15 mA;

R7 = 68 k

Variation of G

with frequency,

referred to 0.8 kHz

f = 300 and 3400 Hz

0.5

0.1

0.5

Variation of G

with temperature,

referred to 25

without R6;

line

= 50 mA;

amb

25 to

0.2

DTMF input (pin 12)

Input impedance

16.8

20.7

24.6

Voltage gain (see Fig.22)

line

= 15 mA;

R7 = 68 k

Variation of G

with frequency,

referred to 0.8 kHz

f = 300 and 3400 Hz

0.5

0.1

0.5

f = 697 and 1633 Hz

0.2

0.05

0.2

Variation of G

with temperature,

referred to 25

line

= 50 mA;

amb

25 to

0.2

0.5

Gain adjustment inputs GAS1, GAS2
(pins 2, 3)

Transmitting amplifier,

gain adjustment range

Sending amplifier output LN (pin 1)

Dynamic limiter

Output voltage swing

(peak-to-peak value)

line

= 15 mA;

R7 = 68 k

;

= 0 mA;

i(rms)

= 3.6 mV

LN(p-p)

3.6

4.0

4.5

Total harmonic distortion

= 3.6 mV

10 dB

THD

1.5

2.0

= 3.6 mV

15 dB

THD

2.8

10.0

Output voltage swing

(peak-to-peak value)

= 3.6 mV

10 dB

= 2 mA

LN(p-p)

3.7

3.95

4.2

= 4 mA

LN(p-p)

3.0

3.25

3.5

= 0 mA;

line

= 7 mA

LN(p-p)

= 0 mA;

line

= 4 mA

LN(p-p)

PARAMETER

CONDITIONS

SYMBOL

MIN.

TYP.

MAX.

UNIT

March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

Dynamic behaviour of limiter

C16 = 470 nF

attack time, V

mic

jumps from

2 mV to 40 mV

att

1.5

5.0

release time, V

mic

jumps from

40 mV to 2 mV

rel

150

Noise output voltage (RMS value)

line

= 15 mA;

R7 = 68 k

;

200

between

MIC

and MIC

;

psophometrically

weighted (P53 curve)

no(rms)

dBmp

Receiving amplifier input IR (pin 13)

Input impedance

Receiving amplifier outputs QR

(pins 4, 5)

Output impedance

single-ended

Voltage gain

Fig.23;

line

= 15 mA;

R4 = 100 k

single-ended; R

= 300

differential; R

= 600

Variation with frequency,

referred to 0.8 kHz

f = 300 and 3400 Hz

0.5

0.2

Variation with temperature,

referred to 25

without R6;

line

= 50 mA;

amb

25 to

0.2

Output voltage (RMS value)

THD = 2%;

sinewave drive;

R4 = 100 k

;

line

= 15 mA

single-ended; R

= 150

= 0 mA

o(rms)

0.22

= 2 mA

o(rms)

0.35

differential; R

= 450

= 0 mA

o(rms)

0.39

= 2 mA

o(rms)

0.64

differential; C

= 47 nF;

(100

series resistor); f = 3400 Hz

= 0 mA

o(rms)

0.57

= 2 mA

o(rms)

0.9

PARAMETER

CONDITIONS

SYMBOL

MIN.

TYP.

MAX.

UNIT

March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

Output voltage (RMS value)

= 0 mA;

THD = 10%;

sinewave drive;

R4 = 100 k

;

single-ended;

= 150

;

line

= 4 mA

o(rms)

line

= 7 mA

o(rms)

160

Noise output voltage (RMS value)

line

= 15 mA;

= 100 k

;

psophometrically

weighted

(P53 curve);

pin IR open

single-ended;

= 300

;

no(rms)

differential;

= 600

no(rms)

Noise output voltage (RMS value)

in circuit of Fig.23;

S1 in position 2;

200

between

MIC

and MIC

;

single-ended;

= 300

= 68 k

no(rms)

100

= 24.9 k

no(rms)

Gain adjustment input GAR (pin 6)

Receiving amplifier,

gain adjustment range

MUTE INPUT (pin 14)

Input voltage HIGH

1.5

SLPE

CC1

0.4

Input voltage LOW

0.3

SLPE

Input current

mute

Change of microphone amplifier

gain at mute-ON

MUTE = HIGH

100

PARAMETER

CONDITIONS

SYMBOL

MIN.

TYP.

MAX.

UNIT

March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

Voltage gain from input

DTMF-SLPE to QR

output

with mute-ON

MUTE = HIGH;
single-ended load;
R

= 300

Power-down input PD (pin 15)

Input voltage HIGH

1.5

SLPE

CC1

0.4

Input voltage LOW

0.3

SLPE

Input current

Automatic gain control input AGC
(pin 18)

Controlling the gain from

IR (pin 13) to QR

, QR

(pins 4, 5) and the gain

from MIC

, MIC

(pins 8, 9)

to LN (pin 1)

R6 = 93.1 k

(between pins
18 and 11)

gain control range with respect to

line

= 15 mA

line

= 75 mA

5.7

6.1

6.5

Highest line current

for maximum gain

line

Lowest line current

for minimum gain

line

Change of gain

between I

line

= 15 and 35 mA

0.9

1.4

1.9

Microphone mute

input DLS/MMUTE (pin 7)

Input voltage low

0.3

Input current at low

input voltage

Release time after a low

level on pin 7

C16 = 470 nF

rel

Change of microphone amplifier

gain at low input voltage on

pin 7

100

PARAMETER

CONDITIONS

SYMBOL

MIN.

TYP.

MAX.

UNIT

March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

APPLICATION INFORMATION

The basic application circuit is shown in Fig.24 and some typical applications are shown in Figs 25, 26 and 27.

In the basic application, the circuit provides two possibilities for supplies to peripheral circuits:

regulated line voltage V

(stabilized V

LN-SLPE

) and unregulated supply voltage for peripheral circuits, the supply

voltage is dependent only on the peripheral supply current. This application is the same as that used for
TEA1060/TEA1061, TEA1067 and TEA1068;

stabilized supply voltage for peripherals (V

CC2-SLPE

), the DC line voltage depends on the current flowing to the

peripheral circuits.

handbook, full pagewidth

MGR077

VEE

REG

AGC

STAB

VCC1

R9
20

820

220

DLS/MMUTE

MUTE

DTMF

MIC

620

TEA1064A

100

RL
600

Iline

C4
100 pF

C7 1 nF

11 to

140 mA

100

C15
220

100

100 nF

R5
3.6
k

R3
3.92 k

390

130

470

C16
470 nF

SLPE

C6
100 pF

130 k

392

R15

GAR

GAS1

GAS2

VCC2

R16

Fig.23 Test circuit for defining voltage gain of the receiving amplifier, voltage gain (G

) is defined as

20 log

/ V

(with S1 in position 1).

March

1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit

with dialler interface and transmit level dynamic limiting

TEA1064A

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pagewidth

MGR078

VEE

REG

GAS2

GAS1

100 pF

AGC

STAB

VCC1

VCC2

392

R15

620

390

R5
3.6
k

100 k

DLS/MMUTE

GAR

MIC

TEA1064A

R7
68
k

C16
470
nF

SLPE

R17
3.3 k

R16
56

R14

R13

100 nF

Zbal

C3
470
nF

C15
220

100

C4
100 pF

1 nF

3.92 k

R2
130 k

R10
13

BAS11

)

BZW14

)

telephone

line

DTMF

MUTE

from dial

and

control circuits

Fig.24 Basic application of the TEA1064A with stabilized supply for peripherals, shown here with a piezo-electric earpiece and DTMF dialling.

The diode bridge and R10 limit the current into, and the voltage across, the circuit during line transients. A different protection
arrangement is required for pulse dialling or register recall.

March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

UNIT

max.

(1)

REFERENCES

OUTLINE

VERSION

EUROPEAN

PROJECTION

ISSUE DATE

IEC

JEDEC

EIAJ

inches

2.65

0.30
0.10

2.45
2.25

0.49
0.36

0.32
0.23

13.0
12.6

7.6
7.4

1.27

10.65
10.00

1.1
1.0

0.9
0.4

8
0

0.25

0.1

DIMENSIONS (inch dimensions are derived from the original mm dimensions)

Note

1. Plastic or metal protrusions of 0.15 mm maximum per side are not included.

1.1
0.4

SOT163-1

detail X

0.25

075E04

MS-013AC

pin 1 index

0.10

0.012
0.004

0.096
0.089

0.019
0.014

0.013
0.009

0.51
0.49

0.30
0.29

0.050

1.4

0.055

0.419
0.394

0.043
0.039

0.035
0.016

0.01

0.25

0.01

0.004

0.043
0.016

0.01

10 mm

scale

(A )

SO20: plastic small outline package; 20 leads; body width 7.5 mm

SOT163-1

95-01-24
97-05-22

March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

SOLDERING

Introduction

There is no soldering method that is ideal for all IC
packages. Wave soldering is often preferred when
through-hole and surface mounted components are mixed
on one printed-circuit board. However, wave soldering is
not always suitable for surface mounted ICs, or for
printed-circuits with high population densities. In these
situations reflow soldering is often used.

This text gives a very brief insight to a complex technology.
A more in-depth account of soldering ICs can be found in
our

"Data Handbook IC26; Integrated Circuit Packages"

(order code 9398 652 90011).

DIP

OLDERING BY DIPPING OR BY WAVE

The maximum permissible temperature of the solder is
260

C; solder at this temperature must not be in contact

with the joint for more than 5 seconds. The total contact
time of successive solder waves must not exceed
5 seconds.

The device may be mounted up to the seating plane, but
the temperature of the plastic body must not exceed the
specified maximum storage temperature (T

stg max

). If the

printed-circuit board has been pre-heated, forced cooling
may be necessary immediately after soldering to keep the
temperature within the permissible limit.

EPAIRING SOLDERED JOINTS

Apply a low voltage soldering iron (less than 24 V) to the
lead(s) of the package, below the seating plane or not
more than 2 mm above it. If the temperature of the
soldering iron bit is less than 300

C it may remain in

contact for up to 10 seconds. If the bit temperature is
between 300 and 400

C, contact may be up to 5 seconds.

EFLOW SOLDERING

Reflow soldering techniques are suitable for all SO
packages.

Reflow soldering requires solder paste (a suspension of
fine solder particles, flux and binding agent) to be applied
to the printed-circuit board by screen printing, stencilling or
pressure-syringe dispensing before package placement.

Several techniques exist for reflowing; for example,
thermal conduction by heated belt. Dwell times vary
between 50 and 300 seconds depending on heating
method. Typical reflow temperatures range from
215 to 250

Preheating is necessary to dry the paste and evaporate
the binding agent. Preheating duration: 45 minutes at
45

AVE SOLDERING

Wave soldering techniques can be used for all SO
packages if the following conditions are observed:

A double-wave (a turbulent wave with high upward
pressure followed by a smooth laminar wave) soldering
technique should be used.

The longitudinal axis of the package footprint must be
parallel to the solder flow.

The package footprint must incorporate solder thieves at
the downstream end.

During placement and before soldering, the package must
be fixed with a droplet of adhesive. The adhesive can be
applied by screen printing, pin transfer or syringe
dispensing. The package can be soldered after the
adhesive is cured.

Maximum permissible solder temperature is 260

C, and

maximum duration of package immersion in solder is
10 seconds, if cooled to less than 150

C within

6 seconds. Typical dwell time is 4 seconds at 250

A mildly-activated flux will eliminate the need for removal
of corrosive residues in most applications.

EPAIRING SOLDERED JOINTS

Fix the component by first soldering two diagonally-
opposite end leads. Use only a low voltage soldering iron
(less than 24 V) applied to the flat part of the lead. Contact
time must be limited to 10 seconds at up to 300

C. When

using a dedicated tool, all other leads can be soldered in
one operation within 2 to 5 seconds between
270 and 320

March 1994

Philips Semiconductors

Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

TEA1064A

DEFINITIONS

LIFE SUPPORT APPLICATIONS

These products are not designed for use in life support appliances, devices, or systems where malfunction of these
products can reasonably be expected to result in personal injury. Philips customers using or selling these products for
use in such applications do so at their own risk and agree to fully indemnify Philips for any damages resulting from such
improper use or sale.

Data sheet status

Objective specification

This data sheet contains target or goal specifications for product development.

Preliminary specification

This data sheet contains preliminary data; supplementary data may be published later.

Product specification

This data sheet contains final product specifications.

Limiting values

Limiting values given are in accordance with the Absolute Maximum Rating System (IEC 134). Stress above one or
more of the limiting values may cause permanent damage to the device. These are stress ratings only and operation
of the device at these or at any other conditions above those given in the Characteristics sections of the specification
is not implied. Exposure to limiting values for extended periods may affect device reliability.

Application information

Where application information is given, it is advisory and does not form part of the specification.

Internet: http://www.semiconductors.philips.com

Philips Semiconductors a worldwide company

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The information presented in this document does not form part of any quotation or contract, is believed to be accurate and reliable and may be changed
without notice. No liability will be accepted by the publisher for any consequence of its use. Publication thereof does not convey nor imply any license
under patent- or other industrial or intellectual property rights.

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Vietnam: see Singapore

Yugoslavia: PHILIPS, Trg N. Pasica 5/v, 11000 BEOGRAD,
Tel. +381 11 625 344, Fax.+381 11 635 777

For all other countries apply to: Philips Semiconductors,
International Marketing & Sales Communications, Building BE-p, P.O. Box 218,
5600 MD EINDHOVEN, The Netherlands, Fax. +31 40 27 24825

Argentina: see South America

Australia: 34 Waterloo Road, NORTH RYDE, NSW 2113,
Tel. +61 2 9805 4455, Fax. +61 2 9805 4466

Austria: Computerstr. 6, A-1101 WIEN, P.O. Box 213, Tel. +43 160 1010,
Fax. +43 160 101 1210

Belarus: Hotel Minsk Business Center, Bld. 3, r. 1211, Volodarski Str. 6,
220050 MINSK, Tel. +375 172 200 733, Fax. +375 172 200 773

Belgium: see The Netherlands

Brazil: see South America

Bulgaria: Philips Bulgaria Ltd., Energoproject, 15th floor,
51 James Bourchier Blvd., 1407 SOFIA,
Tel. +359 2 689 211, Fax. +359 2 689 102

Canada: PHILIPS SEMICONDUCTORS/COMPONENTS,
Tel. +1 800 234 7381

China/Hong Kong: 501 Hong Kong Industrial Technology Centre,
72 Tat Chee Avenue, Kowloon Tong, HONG KONG,
Tel. +852 2319 7888, Fax. +852 2319 7700

Colombia: see South America

Czech Republic: see Austria

Denmark: Prags Boulevard 80, PB 1919, DK-2300 COPENHAGEN S,
Tel. +45 32 88 2636, Fax. +45 31 57 0044

Finland: Sinikalliontie 3, FIN-02630 ESPOO,
Tel. +358 9 615800, Fax. +358 9 61580920

France: 51 Rue Carnot, BP317, 92156 SURESNES Cedex,
Tel. +33 1 40 99 6161, Fax. +33 1 40 99 6427

Germany: Hammerbrookstraße 69, D-20097 HAMBURG,
Tel. +49 40 23 53 60, Fax. +49 40 23 536 300

Greece: No. 15, 25th March Street, GR 17778 TAVROS/ATHENS,
Tel. +30 1 4894 339/239, Fax. +30 1 4814 240

Hungary: see Austria

India: Philips INDIA Ltd, Band Box Building, 2nd floor,
254-D, Dr. Annie Besant Road, Worli, MUMBAI 400 025,
Tel. +91 22 493 8541, Fax. +91 22 493 0966

Indonesia: PT Philips Development Corporation, Semiconductors Division,
Gedung Philips, Jl. Buncit Raya Kav.99-100, JAKARTA 12510,
Tel. +62 21 794 0040 ext. 2501, Fax. +62 21 794 0080

Ireland: Newstead, Clonskeagh, DUBLIN 14,
Tel. +353 1 7640 000, Fax. +353 1 7640 200

Israel: RAPAC Electronics, 7 Kehilat Saloniki St, PO Box 18053,
TEL AVIV 61180, Tel. +972 3 645 0444, Fax. +972 3 649 1007

Italy: PHILIPS SEMICONDUCTORS, Piazza IV Novembre 3,
20124 MILANO, Tel. +39 2 6752 2531, Fax. +39 2 6752 2557

Japan: Philips Bldg 13-37, Kohnan 2-chome, Minato-ku,
TOKYO 108-8507, Tel. +81 3 3740 5130, Fax. +81 3 3740 5077

Korea: Philips House, 260-199 Itaewon-dong, Yongsan-ku, SEOUL,
Tel. +82 2 709 1412, Fax. +82 2 709 1415

Malaysia: No. 76 Jalan Universiti, 46200 PETALING JAYA, SELANGOR,
Tel. +60 3 750 5214, Fax. +60 3 757 4880

Mexico: 5900 Gateway East, Suite 200, EL PASO, TEXAS 79905,
Tel. +9-5 800 234 7381

Printed in The Netherlands

415102/00/02/pp36

Date of release: March 1994

Document order number:

9397 750 nnnnn

Document Outline

Ð­Ð»ÐµÐºÑ‚Ñ€Ð¾Ð½Ð½Ñ‹Ð¹ ÐºÐ¾Ð¼Ð¿Ð¾Ð½ÐµÐ½Ñ‚: TEA1064AT/C2

Document Outline

ÐÐ»ÐµÐºÑ‚Ñ€Ð¾Ð½Ð½Ñ‹Ð¹ ÐºÐ¾Ð¼Ð¿Ð¾Ð½ÐµÐ½Ñ‚: TEA1064AT/C2