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FEATURES
APPLICATIONS
DESCRIPTION
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
6-A, 2.2-V to 5.5-V INPUT, NON-ISOLATED,
WIDE-OUTPUT, ADJUSTABLE POWER MODULE WITH TurboTransTM
Up to 6-A Output Current
TurboTransTM Technology
2.2-V to 5.5-V Input Voltage
Designed to meet Ultra-Fast Transient
Requirements up to 300 A/
s
Wide-Output Voltage Adjust (0.69 V to 3.6 V)
SmartSync Technology
1.5% Total Output Voltage Variation
Efficiencies up to 96%
Output Overcurrent Protection
Complex Multi-Voltage Systems
(Nonlatching, Auto-Reset)
Microprocessors
Operating Temperature: 40
C to 85
C
Bus Drivers
Safety Agency Approvals: (Pending)
UL60950, CSA 22.2 950, EN60950 VDE
Prebias Startup
On/Off Inhibit
Differential Output Voltage Remote Sense
Adjustable Undervoltage Lockout
Auto-TrackTM Sequencing
Ceramic Capacitor Version (PTH04T231W)
The PTH04T230/231W is a high-performance, 6-A rated, non-isolated power module. This regulator represents
the 2nd generation of the PTH series of power modules which include a reduced footprint and improved
features. The PTH04T231W is optimized to be used in applications requiring all ceramic capacitors.
Operating from an input voltage range of 2.2 V to 5.5 V, the PTH04T230/231W requires a single resistor to set
the output voltage to any value over the range, 0.69 V to 3.6 V. The wide input voltage range makes the
PTH04T230/231W particularly suitable for advanced computing and server applications that use a 2.5-V, 3.3-V
or 5-V intermediate bus architecture.
The module incorporates a comprehensive list of features. Output over-current and over-temperature shutdown
protects against most load faults. A differential remote sense ensures tight load regulation. An adjustable
under-voltage lockout allows the turn-on voltage threshold to be customized. Auto-TrackTM sequencing is a
popular feature that greatly simplifies the simultaneous power-up and power-down of multiple modules in a
power system.
The PTH04T230/231W includes new patent pending technologies, TurboTransTM and SmartSync. The
TurboTrans feature optimizes the transient response of the regulator while simultaneously reducing the quantity
of external output capacitors required to meet a target voltage deviation specification. Additionally, for a target
output capacitor bank, TurboTrans can be used to significantly improve the regulators transient response by
reducing the peak voltage deviation. SmartSync allows for switching frequency synchronization of multiple
modules, thus simplifying EMI noise suppression tasks and reduces input capacitor RMS current requirements.
Double-sided surface mount construction provides a low profile and compact footprint. Package options include
both through-hole and surface mount configurations that are lead (Pb) - free and RoHS compatible.
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas
Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
TurboTrans, TMS320 are trademarks of Texas Instruments.
PRODUCTION DATA information is current as of publication date.
Copyright 2006, Texas Instruments Incorporated
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
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R
UVLO
1%
0.05 W
(Optional)
PTH04T230W
2
4
8
7
Track
VoAdj
Vo
TT
3
GND
GND
+Sense
5
L
O
A
D
-Sense
GND
+
10
Inhibit
INH/UVLO
Track
9
6
-Sense
+Sense
Vo
SYNC
1
SmartSync
C
O1
100
F
Ceramic
(Required)
C
O2
150
F
Non-Ceramic
(Required)
V
I
V
I
C
I
330
F
(Required)
(Note B)
R
TT
1%
0.05 W
(Optional)
R
SET
1%
0.05 W
(Required)
(Note A)
TurboTrans
E
UDG-06046
+
R
UVLO
1%
0.05 W
(Optional)
PTH04T231W
2
4
8
7
Track
VoAdj
Vo
TT
3
GND
GND
+Sense
5
L
O
A
D
-Sense
GND
10
Inhibit
INH/UVLO
Track
9
6
-Sense
+Sense
Vo
SYNC
1
SmartSync
C
O
300
F
Ceramic
(Required)
V
I
V
I
C
I
300
F
(Required)
R
TT
1%
0.05 W
(Optional)
R
SET
1%
0.05 W
(Required)
(Note A)
TurboTrans
E
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
PTH04T230W
A.
R
SET
required to set the output voltage to a value higher than 0.69 V. See the Electrical Characteristics table.
B.
An additional 22-
F ceramic input capacitor is recommended to reduce RMS ripple current.
PTH04T231W - Ceramic Capacitor Version
2
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DATASHEET TABLE OF CONTENTS
ENVIRONMENTAL AND ABSOLUTE MAXIMUM RATINGS
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
ORDERING INFORMATION
For the most current package and ordering information, see the Package Option Addendum at the end of this data sheet, or see
the TI website at www.ti.com.
DATASHEET SECTION
PAGE NUMBER
ENVIRONMENTAL AND ABSOLUTE MAXIMUM RATINGS
3
ELECTRICAL CHARACTERISTICS TABLE (PTH04T230W)
4
ELECTRICAL CHARACTERISTICS TABLE (PTH04T231W)
6
PIN-OUT AND TERMINAL FUNCTIONS
8
TYPICAL CHARACTERISTICS (V
I
= 5V)
9
TYPICAL CHARACTERISTICS (V
I
= 3.3V)
10
ADJUSTING THE OUTPUT VOLTAGE
11
CAPACITOR RECOMMENDATIONS
13
TURBOTRANSTM INFORMATION
17
UNDERVOLTAGE LOCKOUT (UVLO)
22
SOFT-START POWER-UP
23
REMOTE SENSE
23
OUTPUT ON/OFF INHIBIT
24
OVER-CURRENT PROTECTION
24
OVER-TEMPERATURE PROTECTION
25
SYCHRONIZATION (SMARTSYNC)
25
AUTO-TRACK SEQUENCING
26
PREBIAS START-UP
28
TAPE & REEL AND TRAY DRAWINGS
30
(Voltages are with respect to GND)
UNIT
V
Track
Track pin voltage
0.3 to V
I
+ 0.3
V
T
A
Operating temperature range Over V
I
range
40 to 85
Surface temperature of module body or pins
T
wave
Wave soldering temperature
AH and AD suffix
260
(5 seconds maximum)
C
AS suffix
235
(1)
T
reflow
Solder reflow temperature
Surface temperature of module body or pins
AZ suffix
260
(1)
T
stg
Storage temperature
40 to 125
(2)
Mechanical shock
Suffix AH and AD
500
Per Mil-STD-883D, Method 2002.3 1 msec,
1/2 sine, mounted
Suffix AS and AZ
250
G
Suffix AH and AD
20
Mechanical vibration
Mil-STD-883D, Method 2007.2 20-2000 Hz
Suffix AS and AZ
15
Weight
2.7
grams
Flammability
Meets UL94V-O
(1)
During reflow of surface mount package version do not elevate peak temperature of the module, pins or internal components above the
stated maximum.
(2)
The shipping tray or tape & reel cannot be used to bake parts at temperatures higher than 65C.
3
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ELECTRICAL CHARACTERISTICS
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
PTH04T230W
T
A
=25
C, V
I
= 5 V, V
O
= 3.3 V, C
I
= 330 F, C
O
1 = 100 F ceramic, C
O
2 = 150 F non-ceramic, and I
O
= I
O
max (unless
otherwise stated)
PARAMETER
TEST CONDITIONS
PTH04T230W
UNIT
MIN
TYP
MAX
I
O
Output current
Over V
O
range
25
C, natural convection
0
6
A
0.69
V
O
1.7
2.2
5.5
V
I
Input voltage range
Over I
O
range
V
1.7 < V
O
3.6
V
O
+0.5
(1)
5.5
Output adjust range
Over I
O
range
0.69
3.6
V
Set-point voltage tolerance
0.5
1.0
(2)
%V
o
Temperature variation
40
C < T
A
< 85
C
0.3
%V
o
V
O
Line regulaltion
Over V
I
range
2
mV
Load regulation
Over I
O
range
2
mV
Total output variation
Includes set-point, line, load, 40
C
T
A
85
C
1.5
(2)
%V
O
R
SET
= 1.21 k
, V
O
= 3.3 V
94%
R
SET
= 2.38 k
, V
O
= 2.5 V
92%
R
SET
= 4.78 k
, V
O
= 1.8 V
90%
Efficiency
I
O
= 6 A
R
SET
= 7.09 k
, V
O
= 1.5 V
89%
R
SET
= 12.1 k
, V
O
= 1.2 V
87%
R
SET
= 20.8 k
, V
O
= 1.0 V
85%
R
SET
= 689 k
, V
O
= 0.7 V
81%
V
O
Ripple (peak-to-peak)
20-MHz bandwidth
1
%V
O
I
LIM
Overcurrent threshold
Reset, followed by auto-recovery
10
A
w/o TurboTrans
Recovery Time
100
Sec
C
O
1 = 100
F, ceramic
C
O
2 = 150
F,
V
O
Overshoot
100
mV
non-ceramic
2.5 A/s load step
w/o TurboTrans
(3)
Recovery Time
120
Sec
50% to 100% I
O
max
Transient response
C
O
1 = 100
F, ceramic
V
I
= 3.3 V
V
O
Overshoot
60
mV
C
O
2 = 990
F, Type B
V
O
= 2.5 V
with TurboTrans
Recovery Time
180
Sec
C
O
1 = 100
F, ceramic
C
O
2 = 990
F, Type B
V
O
Overshoot
35
mV
R
TT
= 1.54 k
I
IL
Track input current (pin 9)
Pin to GND
-130
(4)
A
dV
track
/dt
Track slew rate capability
C
O
C
O
(max)
1
V/ms
V
I
increasing, R
UVLO
= OPEN
1.95
2.19
Adjustable Under-voltage lockout
UVLO
ADJ
V
I
decreasing, R
UVLO
= OPEN
1.3
1.5
V
(pin 10)
Hysteresis, R
UVLO
52.3 k
0.5
Input high voltage (V
IH
)
Open
(5)
V
Inhibit control (pin 10)
Input low voltage (V
IL
)
-0.2
0.6
Input low current (I
IL
), Pin 10 to GND
125
A
I
in
Input standby current
Inhibit (pin 10) to GND, Track (pin 9) open
5
mA
f
s
Switching frequency
Over V
I
and I
O
ranges, SmartSync (pin 1) to GND
300
kHz
f
SYNC
Synchronization (SYNC) frequency
240
400
kHz
V
SYNCH
SYNC High-Level Input Voltage
2
5.5
V
V
SYNCL
SYNC Low-Level Input Voltage
0.8
V
t
SYNC
SYNC Minimum Pulse Width
200
nSec
(1)
The minimum input voltage is 2.2 V or (V
O
+ 0.5) V, whichever is greater.
(2)
The set-point voltage tolerance is affected by the tolerance and stability of R
SET
. The stated limit is unconditionally met if R
SET
has a
tolerance of 1% with 200 ppm/C or better temperature stability.
(3)
Without TurboTrans, the minimum ESR limit of 7 m
must not be violated.
(4)
A low-leakage (<100 nA), open-drain device, such as MOSFET or voltage supervisor IC, is recommended to control pin 9. The
open-circuit voltage is less than V
I
.
(5)
This control pin has an internal pull-up. Do not place an external pull-up on this pin. If it is left open-circuit, the module operates when
input power is applied. A small, low-leakage (<100 nA) MOSFET is recommended for control. The open-circuit voltage is less than 3.5
Vdc. For additional information, see the related application information section.
4
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PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
ELECTRICAL CHARACTERISTICS (continued)
PTH04T230W
T
A
=25
C, V
I
= 5 V, V
O
= 3.3 V, C
I
= 330 F, C
O
1 = 100 F ceramic, C
O
2 = 150 F non-ceramic, and I
O
= I
O
max (unless
otherwise stated)
PARAMETER
TEST CONDITIONS
PTH04T230W
UNIT
MIN
TYP
MAX
C
I
External input capacitance
330
(6)
F
Nonceramic
150
(7)
5000
(8)
Capacitance value
F
without
Ceramic
100
(7)
500
TurboTrans
Equivalent series resistance (non-ceramic)
7
m
C
O
External output capacitance
see table
5,000
Capacitance value
F
with
(9)
(10)
Turbotrans
Capacitance
ESR product (C
O
ESR)
1000
10,000
F
m
Per Telcordia SR-332, 50% stress,
MTBF
Reliability
5.3
10
6
Hr
T
A
= 40
C, ground benign
(6)
A 330 F input capacitor is required for proper operation. The capacitor must be rated for a minimum of 400 mA rms of ripple current.
An additional 22-
F ceramic input capacitor is recommended to reduce rms ripple current.
(7)
100 F ceramic and 150 F non-ceramic external output capacitance is required for basic operation. The minimum output capacitance
requirement increases when TurboTransTM (TT) technology is used. See the Application Information for more guidance.
(8)
This is the calculated maximum disregarding TurboTransTM technology. When the TurboTrans feature is used, the minimum output
capacitance must be increased. See the TurboTrans application notes for further guidance.
(9)
When using TurboTransTM technology, a minimum value of output capacitance is required for proper operation. Additionally, low ESR
capacitors are required for proper operation. See the TurboTrans application notes for further guidance.
(10) This is the calaculated maximum when using the TurboTrans feature. Additionally, low ESR capacitors are required for proper operation.
See the TurboTrans application notes for further guidance.
5
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ELECTRICAL CHARACTERISTICS
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
PTH04T231W (Ceramic Capacitors)
T
A
= 25
C, V
I
= 5 V, V
O
= 3.3 V, C
I
= 300 F ceramic, C
O
= 300 F ceramic, and I
O
= I
O
max (unless otherwise stated)
PARAMETER
TEST CONDITIONS
PTH04T231W
UNIT
MIN
TYP
MAX
I
O
Output current
Over V
O
range
25
C, natural convection
0
6
A
0.69
V
O
1.7
2.2
5.5
V
I
Input voltage range
Over I
O
range
V
1.7 < V
O
3.6 V
O
+0.5
(1)
5.5
V
OADJ
Output voltage adjust range
Over I
O
range
0.69
3.6
V
Set-point voltage tolerance
0.5
1
(2)
%V
o
Temperature variation
40
C < T
A
< 85
C
0.3
%V
o
V
O
Line regulaltion
Over V
I
range
2
mV
Load regulation
Over I
O
range
2
mV
Total output variation
Includes set-point, line, load, 40
C
T
A
85
C
1.5
(2)
%V
o
R
SET
= 1.21 k
, V
O
= 3.3 V
94%
R
SET
= 2.38 k
, V
O
= 2.5 V
92%
R
SET
= 4.78 k
, V
O
= 1.8 V
90%
Efficiency
I
O
= 6 A
R
SET
= 7.09 k
, V
O
= 1.5 V
89%
R
SET
= 12.1 k
, V
O
= 1.2 V
87%
R
SET
= 20.8 k
, V
O
= 1.0 V
85%
R
SET
= 689 k
, V
O
= 0.7 V
81%
V
O
Ripple (peak-to-peak)
20-MHz bandwidth
1
%V
O
I
LIM
Overcurrent threshold
Reset, followed by auto-recovery
10
A
Recovery time
100
s
w/o TurboTrans
C
O
= 300
F, Type A
V
O
over/undershoot
70
mV
2.5 A/s load step
w/o TurboTrans
Recovery time
100
s
50 to 100% I
O
max
C
O
= 800
F, Type A
Transient response
mV
V
I
= 3.3 V
V
O
over/undershoot
55
R
TT
= open
V
O
= 2.5 V
w/ TurboTrans
Recovery time
150
s
C
O
= 800
F, Type A
mV
V
O
over/undershoot
35
R
TT
= 11.3 k
I
IL
Track input current (pin 9)
Pin to GND
130
(3)
A
dV
track
/dt
Track slew rate capability
C
O
C
O
(max)
1
V/ms
V
I
increasing, R
UVLO
= OPEN
1.95
2.19
Adjustable Under-voltage lockout
UVLO
ADJ
V
i
decreasing, R
UVLO
= OPEN
1.3
1.5
V
(pin 10)
Hysteresis, R
UVLO
= OPEN
0.5
Input high voltage (V
IH
)
Open
(4)
V
Inhibit control (pin 10)
Input low voltage (V
IL
)
-0.2
0.8
Input low current (I
IL
), Pin 10 to GND
-235
A
I
in
Input standby current
Inhibit (pin 10) to GND, Track (pin 9) open
5
mA
f
s
Switching frequency
Over V
I
and I
O
ranges, SmartSync (pin 1) to GND
300
kHz
Synchronization (SYNC)
f
SYNC
240
400
kHz
frequency
V
SYNCH
SYNC High-Level Input Voltage
2
5.5
V
V
SYNCL
SYNC Low-Level Input Voltage
0.8
V
t
SYNC
SYNC Minimum Pulse Width
200
nSec
C
I
External input capacitance
Ceramic
300
(5)
F
(1)
The minimum input voltage is 2.2 V or (V
O
+ 0.5) V, whichever is greater.
(2)
The set-point voltage tolerance is affected by the tolerance and stability of R
SET
. The stated limit is unconditionally met if R
SET
has a
tolerance of 1% with 100 ppm/C or better temperature stability. .
(3)
A low-leakage (<100 nA), open-drain device, such as MOSFET or voltage supervisor IC, is recommended to control pin 9. The
open-circuit voltage is less than V
I
.
(4)
This control pin has an internal pull-up. Do not place an external pull-up on this pin. If it is left open-circuit, the module operates when
input power is applied. A small, low-leakage (<100 nA) MOSFET is recommended for control. The open-circuit voltage is less than 3.5
Vdc. For additional information, see the related application note.
(5)
300 F of ceramic input capacitance is required for proper operation.
6
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PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
ELECTRICAL CHARACTERISTICS (continued)
PTH04T231W (Ceramic Capacitors)
T
A
= 25
C, V
I
= 5 V, V
O
= 3.3 V, C
I
= 300 F ceramic, C
O
= 300 F ceramic, and I
O
= I
O
max (unless otherwise stated)
PARAMETER
TEST CONDITIONS
PTH04T231W
UNIT
MIN
TYP
MAX
w/o TurboTrans
Capacitance Value
Ceramic
300
(6)
5000
(7)
F
see table
C
O
External output capacitance
Capacitance Value
5000
F
(6)
w/ TurboTrans
Capacitance
ESR product (C
O
ESR)
100
1000
F
m
Per Telcordia SR-332, 50% stress,
MTBF
Reliability
5.3
10
6
Hr
T
A
= 40
C, ground benign
(6)
300 F of ceramic output capacitance is required for basic operation. The minimum output capacitance requirement increases when
TurboTransTM (TT) technology is utilized. Additionally, low ESR capacitors are required for proper operation. See related Application
Information for more guidance.
(7)
This is the calculated maximum disregarding TurboTransTM technology.
7
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1
10
9
7
6
5
4
3
8
2
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
PTH04T230/231W
(TOP VIEW)
TERMINAL FUNCTIONS
TERMINAL
DESCRIPTION
NAME
NO.
V
I
2
The positive input voltage power node to the module, which is referenced to common GND.
V
O
4
The regulated positive power output with respect to the GND.
This is the common ground connection for the V
I
and V
O
power connections. It is also the 0 Vdc reference for
GND
3
the control inputs.
The Inhibit pin is an open-collector/drain, negative logic input that is referenced to GND. Applying a low level
ground signal to this input disables the module's output and turns off the output voltage. When the Inhibit control
is active, the input current drawn by the regulator is significantly reduced. If the Inhibit pin is left open-circuit, the
Inhibit and
module produces an output whenever a valid input source is applied.
10
UVLO
(1)
This pin is also used for input undervoltage lockout (UVLO) programming. Connecting a resistor from this pin to
GND (pin 3) allows the ON threshold of the UVLO to be adjusted higher than the default value. For more
information, see the Application Information section.
A 0.05 W 1% resistor must be directly connected between this pin and pin 6 ( Sense) to set the output voltage
to a value higher than 0.69 V. The temperature stability of the resistor should be 100 ppm/
C (or better). The
setpoint range for the output voltage is from 0.69 V to 3.6 V. If left open circuit, the output voltage defaults to its
V
O
Adjust
7
lowest value. For further information, on output voltage adjustment see the related application note.
The specification table gives the preferred resistor values for a number of standard output voltages.
The sense input allows the regulation circuit to compensate for voltage drop between the module and the load.
+ Sense
5
For optimal voltage accuracy, +Sense must be connected to V
O
, close to the load.
The sense input allows the regulation circuit to compensate for voltage drop between the module and the load.
Sense
6
For optimal voltage accuracy, Sense must be connected to GND (pin 3), very close to the module (within 10
cm).
This is an analog control input that enables the output voltage to follow an external voltage. This pin becomes
active typically 20 ms after the input voltage has been applied, and allows direct control of the output voltage
from 0 V up to the nominal set-point voltage. Within this range the module's output voltage follows the voltage at
Track
9
the Track pin on a volt-for-volt basis. When the control voltage is raised above this range, the module regulates
at its set-point voltage. The feature allows the output voltage to rise simultaneously with other modules powered
from the same input bus. If unused, this input should be connected to V
I
.
NOTE: Due to the undervoltage lockout feature, the output of the module cannot follow its own input voltage
during power up. For more information, see the related application note.
This input pin adjusts the transient response of the regulator. To activate the TurboTrans feature, a 1%, 0.05 W
resistor must be connected between this pin and pin 5 (+Sense) very close to the module. For a given value of
output capacitance, a reduction in peak output voltage deviation is achieved by using this feature. If unused, this
TurboTransTM
8
pin must be left open-circuit. The resistance requirement can be selected from the TurboTrans resistor table in
the Application Information section. External capacitance must never be connected to this pin unless the
TurboTrans resistor is a short, 0
.
This input pin sychronizes the switching frequency of the module to an external clock frequency. The SmartSync
feature can be used to sychronize the switching fequency of multiple PTH04T230/231W modules, aiding EMI
SmartSync
1
noise suppression efforts. If unused, this pin should be connected to GND (pin 3). For more information, please
review the Application Information section.
(1)
Denotes negative logic: Open = Normal operation, Ground = Function active
8
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TYPICAL CHARACTERISTICS
(1) (2)
CHARACTERISTIC DATA (V
I
= 5 V)
0
60
1
80
70
2
4
5
6
3
50
100
90
2.5 V
3.3 V
1.8 V
1.5 V
1.0 V
0.7 V
3.3 V
2.5 V
1.8 V
1.5 V
1.2 V
1.0 V
0.7 V
VO
I
O
- Output Current - A
Efficiency - %
V
IN
= 5 V
I
O
- Output Current - A
P
D
- Power Dissipation - W
0
1
2
4
5
6
3
0
0.9
0.6
0.3
1.5
1.2
2.5 V
1.8 V
1.2 V
0.7 V
1.0 V
3.3 V
3.3 V
2.5 V
1.8 V
1.2 V
1.0 V
0.7 V
VO
V
IN
= 5 V
I
O
- Output Current - A
V
O
- Output V
oltage Ripple - V
P
P
(mV)
1.5 V
0
1
2
4
5
6
3
20
16
8
4
24
3.3 V
2.5 V
1.8 V
1.5 V
1.2 V
1.0 V
0.7 V
VO
3.3 V
2.5 V
1.8 V
1.2 V
1.0 V
0.7 V
12
V
IN
= 5 V
I
O
- Output Current - A
P
D
- Ambient T
emperature -
C
Natural
Convection
0
1
2
4
5
6
3
20
60
50
40
30
07
90
80
All V
O
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
EFFICIENCY
OUTPUT RIPPLE
POWER DISSIPATION
vs
vs
vs
OUTPUT CURRENT
OUTPUT CURRENT
OUTPUT CURRENT
Figure 1.
Figure 2.
Figure 3.
AMBIENT TEMPERATURE
vs
OUTPUT CURRENT
Figure 4.
(1)
The electrical characteristic data has been developed from actual products tested at 25C. This data is considered typical for the
converter. Applies to
Figure 1
,
Figure 2
, and
Figure 3
.
(2)
The temperature derating curves represent the conditions at which internal components are at or below the manufacturer's maximum
operating temperatures. Derating limits apply to modules soldered directly to a 100 mm x 100 mm double-sided PCB with 2 oz. copper.
Applies to
Figure 4
.
9
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TYPICAL CHARACTERISTICS
(1) (2)
CHARACTERISTIC DATA (V
I
= 3.3 V)
I
O
- Output Current - A
P
D
- Power Dissipation - W
0
1
2
4
5
6
3
0.1
0.7
0.3
0.9
1.1
VO
2.5 V
1.8 V
1.2 V and 0.7 V
1.0 V
2.5 V
1.8 V
1.0 V
1.2 V and 0.7 V
0.5
V
IN
= 3.3 V
I
O
- Output Current - A
Efficiency - %
0
60
1
80
70
2
4
5
6
3
50
100
90
2.5 V
1.8 V
1.5 V
1.2 V
1.0 V
0.7 V
VO
2.5 V
1.8 V
1.5 V
1.0 V
0.7 V
1.2 V
V
IN
= 3.3 V
I
O
- Output Current - A
V
O
- Output V
oltage Ripple - V
P
P
(mV)
0
1
2
4
5
6
3
10
8
6
14
4
12
VO
2.5 V
1.8 V
1.2 V
1.0 V
0.7 V
2.5 V
1.8 V
1.0 V
0.7 V
1.2 V
V
IN
= 3.3 V
I
O
- Output Current - A
P
D
- Ambient T
emperature -
C
Natural
Convection
0
1
2
4
5
6
3
20
60
50
40
30
07
90
80
All V
O
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
EFFICIENCY
OUTPUT RIPPLE
POWER DISSIPATION
vs
vs
vs
OUTPUT CURRENT
OUTPUT CURRENT
OUTPUT CURRENT
Figure 5.
Figure 6.
Figure 7.
AMBIENT TEMPERATURE
vs
OUTPUT CURRENT
Figure 8.
(1)
The electrical characteristic data has been developed from actual products tested at 25C. This data is considered typical for the
converter. Applies to
Figure 5
,
Figure 6
, and
Figure 7
.
(2)
The temperature derating curves represent the conditions at which internal components are at or below the manufacturer's maximum
operating temperatures. Derating limits apply to modules soldered directly to a 100 mm x 100 mm double-sided PCB with 2 oz. copper.
Applies to
Figure 8
.
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APPLICATION INFORMATION
ADJUSTING THE OUTPUT VOLTAGE
R
SET
+
10 k
W
0.69
V
O
*
0.69
*
1.43 k
W
(1)
UDG-06043
R
SET
1%
0.05 W
V
O
+Sense
-Sense
VoAdj
GND
3
4
5
6
7
+Sense
-Sense
GND
V
O
PTH04T230/231W
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
The V
O
Adjust control (pin 7) sets the output voltage of the PTH04T230/231W. The adjustment range of the
PTH04T230/231W is 0.69 V to 3.6 V. The adjustment method requires the addition of a single external resistor,
R
SET
, that must be connected directly between the V
O
Adjust and the Sense pins.
Table 1
gives the standard
value of the external resistor for a number of standard voltages, along with the actual output voltage that this
resistance value provides.
For other output voltages, the value of the required resistor can either be calculated using the following formula,
or simply selected from the range of values given in
Table 2
.
Figure 9
shows the placement of the required
resistor.
Table 1. Preferred Values of R
SET
for Standard Output Voltages
V
O
(Standard) (V)
R
SET
(Standard Value) (k
)
V
O
(Actual) (V)
3.3
(1)
1.21
3.304
2.5
(1)
2.37
2.506
1.8
(1)
4.75
1.807
1.5
(1)
6.98
1.510
1.2
12.1
1.200
1.0
20.5
1.004
0.7
681
0.700
(1)
The minimum input voltage is 2.2 V or (V
O
+ 0.5) V, whichever is greater.
(1)
R
SET
: Use a 0.05 W resistor with a tolerance of 1% and temperature stability of 100 ppm/
C (or better). Connect the
resistor directly between pins 7 and 6, as close to the regulator as possible, using dedicated PCB traces.
(2)
Never connect capacitors from V
O
Adjust to either GND, V
O
, or +Sense. Any capacitance added to the V
O
Adjust pin
affects the stability of the regulator.
Figure 9. V
O
Adjust Resistor Placement
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PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
Table 2. Output Voltage Set-Point Resistor Values (Standard Values)
V
O
Required (V)
R
SET
(k
)
V
O
Required (V)
R
SET
(k
)
0.70
681
1.80
4.75
0.75
113
1.85
4.53
0.80
61.9
1.90
4.22
0.85
41.2
1.95
4.02
0.90
31.6
2.00
3.83
0.95
24.9
2.10
3.40
1.00
20.5
2.20
3.09
1.05
17.8
2.30
2.87
1.10
15.4
2.40
2.61
1.15
13.7
2.50
2.37
1.20
12.1
2.60
2.15
1.25
10.7
2.70
2.00
1.30
9.88
2.80
1.82
1.35
9.09
2.90
1.69
1.40
8.25
3.00
1.54
1.45
7.68
3.10
1.43
1.50
6.98
3.20
1.33
1.55
6.49
3.30
1.21
1.60
6.04
3.40
1.13
1.65
5.76
3.50
1.02
1.70
5.36
3.60
0.931
1.75
5.11
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CAPACITOR RECOMMENDATIONS FOR THE PTH04T230/231W POWER MODULE
Capacitor Technologies
Input Capacitor (Required)
Input Capacitor Information
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
Electrolytic Capacitors
When using electrolytic capacitors, high-quality, computer-grade electrolytic capacitors are recommended.
Aluminum electrolytic capacitors provide adequate decoupling over the frequency range of 2 kHz to 150
kHz, and are suitable when ambient temperatures are above -20
C. For operation below -20
C, tantalum,
ceramic, or OS-CON type capacitors are required.
Ceramic Capacitors
The performance of aluminum electrolytic capacitors is less effective above 150 kHz. Multilayer ceramic
capacitors have a low ESR and a resonant frequency higher than the bandwidth of the regulator. They can
be used to reduce the reflected ripple current at the input as well as improve the transient response of the
output.
Tantalum, Polymer-Tantalum Capacitors
Tantalum type capacitors may only used on the output bus, and are recommended for applications where
the ambient operating temperature is less than 0
C. The AVX TPS series and Kemet capacitor series are
suggested over many other tantalum types due to their lower ESR, higher rated surge, power dissipation,
and ripple current capability. Tantalum capacitors that have no stated ESR or surge current rating are not
recommended for power applications.
The PTH04T231W requires a minimum input capacitance of 300
F of ceramic type.
The PTH04T230W requires a minimum input capacitance of 330
F. The ripple current rating of the electrolytic
capacitor must be at least 400 mArms. An optional 22-
F X5R/X7R ceramic capacitor is recommended to
reduce the RMS ripple current.
The size and value of the input capacitor is determined by the converter's transient performance capability. This
minimum value assumes that the converter is supplied with a responsive, low-inductance input source. This
source should have ample capacitive decoupling, and be distributed to the converter via PCB power and ground
planes.
Ceramic capacitors should be located as close as possible to the module's input pins, within 0.5 inch (1,3 cm).
Adding ceramic capacitance is necessary to reduce the high-frequency ripple voltage at the module's input. This
reduces the magnitude of the ripple current through the electroytic capacitor, as well as the amount of ripple
current reflected back to the input source. Additional ceramic capacitors can be added to further reduce the
RMS ripple current requirement for the electrolytic capacitor.
Increasing the minimum input capacitance to 680-
F is recommended for high-performance applications, or
wherever the input source performance is degraded.
The main considerations when selecting input capacitors are the RMS ripple current rating, temperature stability,
and maintaining less than 100 m
of equivalent series resistance (ESR).
Regular tantalum capacitors are not recommended for the input bus. These capacitors require a recommended
minimum voltage rating of 2
(maximum dc voltage + ac ripple). This is standard practice to ensure reliability.
No tantalum capacitors were found to have voltage ratings sufficient to meet this requirement.
When the operating temperature is below 0
C, the ESR of aluminum electrolytic capacitors increases. For these
applications, OS-CON, poly-aluminum, and polymer-tantalum types should be considered.
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Output Capacitor (Required)
Output Capacitor Information
TurboTrans Output Capacitance
Non-TurboTrans Output Capacitance
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
The PTH04T231W requires a minimum output capacitance of 300
F of ceramic type.
The PTH04T230W requires a minimum 100
F of ceramic and 150 F of non-ceramic output capacitance.
Additional non-ceramic, low-ESR capacitance is recommended for improved performance. See data sheet for
maximum capacitance limits.
The required capacitance above the minimum is determined by actual transient deviation requirements. See the
TurboTrans Technology application section within this document for specific capacitance selection.
When selecting output capacitors, the main considerations are capacitor type, temperature stability, and ESR.
When using the TurboTrans feature, the capacitance X ESR product should also be considered (see the
following section).
Ceramic output capacitors added for high-frequency bypassing should be located as close as possible to the
load to be effective. Ceramic capacitor values below 10
F should not be included when calculating the total
output capacitance value.
When the operating temperature is below 0
C, the ESR of aluminum electrolytic capacitors increases. For these
applications, OS-CON, poly-aluminum, and polymer-tantalum types should be considered.
TurboTrans allows the designer to optimize the output capacitance according to the system transient design
requirement. High quality, ultra-low ESR capacitors are required to maximize TurboTrans effectiveness. When
using TurboTrans, the capacitor's capacitance (
F)
ESR (m
) product determines its capacitor type; Type A,
B, or C. These three types are defined as follows:
Type A = (100
capacitance
ESR
1000) (e.g. ceramic)
Type B = (1000 < capacitance
ESR
5000) (e.g. polymer-tantalum)
Type C = (5000 < capacitance
ESR
10,000) (e.g. OS-CON)
When using more than one type of output capacitor, select the capacitor type that makes up the majority of the
total output capacitance. When calculating the C
ESR product, use the maximum ESR value from the
capacitor manufacturer's data sheet.
The PTH04T231W should be used when only Type A (ceramic) capacitors are used on the output.
Working Examples:
A capacitor with a capacitance of 330
F and an ESR of 5 m
, has a C
ESR product of 1650
F x m
(330
F
5 m
). This is a Type B capacitor.
A capacitor with a capacitance of 1000
F and an ESR of 8 m
, has a C
ESR product of 8000
F x m
(1000
F
8 m
). This is a Type C capacitor.
See the TurboTrans Technology application section within this document for specific capacitance selection.
Table 3
includes a preferred list of capacitors by type and vendor. See the Output Bus / TurboTrans column.
If the TurboTrans feature is not used, minimum ESR and maximum capacitor limits must be followed. System
stability may be effected and increased output capacitance may be required without TurboTrans.
When using the PTH04T230W without the TurboTrans feature, observe the minimum ESR of the entire output
capacitor bank. The minimum ESR limit of the output capacitor bank is 7 m
. A list of preferred low-ESR type
capacitors, are identified in
Table 3
.
When using the PTH04T231W without the TurboTrans feature, the maximum amount of capacitance is 3000
F
of ceramic type. Large amounts of capacitance may reduce system stability.
Utilizing the TurboTrans feature improves system stability, improves transient response, and reduces
the amount of output capacitance required to meet system transient design requirements.
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Designing for Fast Load Transients
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
The transient response of the dc/dc converter has been characterized using a load transient with a di/dt of
2.5 A/
s. The typical voltage deviation for this load transient is given in the Electrical Characteristics table using
the minimum required value of output capacitance. As the di/dt of a transient is increased, the response of a
converter's regulation circuit ultimately depends on its output capacitor decoupling network. This is an inherent
limitation with any dc/dc converter once the speed of the transient exceeds its bandwidth capability.
If the target application specifies a higher di/dt or lower voltage deviation, the requirement can only be met with
additional low ESR ceramic capacitor decoupling. Generally, with load steps greater than 100 A/
s, adding
multiple 10-
F ceramic capacitors plus 10
1
F, and numerous high frequency ceramics (
0.1
F) is all that is
required to soften the transient higher frequency edges. The PCB location of these capacitors in relation to the
load is critical. DSP, FPGA and ASIC vendors identify types, location and amount of capacitance required for
optimum performance. Low impedance buses, unbroken PCB copper planes, and components located as close
as possible to the high frequency devices are essential for optimizing transient performance.
Table 3. Input/Output Capacitors
(1)
Capacitor Characteristics
Quantity
Max
Output Bus
(2)
Max
Ripple
Capacitor Vendor,
Working
ESR
Turbo-
Value
Current
Physical
Input
Type Series (Style)
No
Voltage
at 100
Vendor Part No.
Trans
(
F)
at 85
C
Size (mm)
Bus
Turbo-
(V)
kHz
Capacitor
(Irms)
Trans
(m
)
Type
(3)
(mA)
Panasonic
SP series (UE)
6.3
220
15
3000
7,3
4,3
2
1
2
B
1
(3)
EEFUE0J221R
FC (Radial )
6.3
390
117
555
8 X 11,5
1
1
N/R
(4)
EEUFC0J391
FK (SMD)
6.3
470
160
600
10 X 10,2
1
1
N/R
(4)
EEVFK0J471P
United Chemi-Con
PTB, Poly-Tantalum(SMD)
6.3
330
25
2600
7,3
4,3
2,8
1
1
3
C
2
(3)
6PTB337MD6TER
LXZ, Aluminum (Radial)
6.3
680
120
555
8 X 12
1
1
N/R
(4)
LXZ6.3VB681M8X12LL
PS, Poly-Alum (Radial)
6.3
390
12
4770
8 X 11,5
1
1
B
2
(3)
6PS390MH11
PT Poly-Tantalum (SMD)
6.3
330
40
3000
7,3
4,3
1
1
N/R
(4)
6PT337MD8TER
MVY, Aluminum SMD)
10
680
150
670
10
10
1
1
B
2
(3)
MVY10VC681MJ10TP
PXA, Poly-Alum (Radial)
10 V
330
14
4420
8
12,2
1
1
2
B
1
(3)
PXA10VC331MH12
Nichicon, Aluminum
WG (SMD)
10
470
150
670
10
10
1
1
N/R
(4)
UWG1A471MNR1GS
HD (Radial)
10
470
72
760
8 X 11,5
1
1
N/R
(4)
UHD1A471MPR
Panasonic, Poly-Aluminum
SE Series (SMD)
2.0
560
5
4000
7,3
4,3
4,2
N/R
(5)
N/R
(6)
B
2
(3)
EEFSE0J561R(V
O
1.6V)
(7)
(1)
Capacitor Supplier Verification
Please verify availability of capacitors identified in this table. Capacitor suppliers may recommend alternative part numbers because of
limited availability or obsolete products.
RoHS, Lead-free and Material Details
See the capacitor suppliers regarding material composition, RoHS status, lead-free status, and manufacturing process requirements.
Component designators or part number deviations can occur when material composition or soldering requirements are updated.
(2)
Additional output capacitance must include the required 100
F of ceramic type.
(3)
Required capacitors with TurboTrans. See the TurboTrans Application information for Capacitor Selection
Capacitor Types:
Type A = (100 < capacitance
ESR
1000)
Type B = (1,000 < capacitance
ESR
5,000)
Type C = (5,000 < capacitance
ESR
10,000)
(4)
Aluminum Electrolytic capacitor not recommended for the TurboTrans due to higher ESR
capacitance products. Aluminum and higher
ESR capacitors can be used in conjunction with lower ESR capacitance.
(5)
N/R Not recommended. The voltage rating does not meet the minimum operating limits.
(6)
N/R Not recommended. The ESR value of this capacitor is below the required minimum when not using TurboTrans.
(7)
The voltage rating of this capacitor only allows it to be used for output voltage that is equal to or less than 80% of the working voltage.
15
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PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
Table 3. Input/Output Capacitors (continued)
Capacitor Characteristics
Quantity
Max
Output Bus
(2)
Max
Ripple
Capacitor Vendor,
Working
ESR
Turbo-
Value
Current
Physical
Input
Type Series (Style)
No
Voltage
at 100
Vendor Part No.
Trans
(
F)
at 85
C
Size (mm)
Bus
Turbo-
(V)
kHz
Capacitor
(Irms)
Trans
(m
)
Type
(3)
(mA)
Sanyo
TPE, POSCAP (SMD)
10
330
25
3300
7,3
4,3
1
1
3
C
1
(8)
10TPE330MF
TPE, POSCAP (SMD)
2.5
470
7
4400
7,3
4,3
N/R
(9)
1
B
2
(8)
2R5TPE470M7(V
O
1.8V)
(10)
TPD, POSCAP (SMD)
2.5
1000
5
6100
7,3
4,3
N/R
(9)
N/R
(11)
B
1
(8)
2R5TPD1000M5(V
O
1.8V)
(10)
SEP, OS-CON (Radial)
6.3
470
15
4210
10
12
1
1
2
C
1
(8)
6SEP470M
SVPA, OS-CON (Radial)
6.3
470
19
4130
10
7,9
1
1
2
C
2
(8)
6SVPA470M
SVP, OS-CON (SMD)
10
330
25
3700
10
7,9
1
1
3
C
1
(8)
10SVP330MX
AVX, Tantalum
TPM Multianode
10
330
23
3000
7,3
4,3
4,1
1
1
3
C
2
(8)
TPME337M010R0035
TPS Series III (SMD)
10
330
40
1830
7,3
4,3
4,1
1
1
6
N/R
(12)
TPSE337M010R0040
TPS Series III (SMD)
4
1000
25
2400
7,3
6,1
3.5
N/R
(9)
1
5
N/R
(12)
TPSV108K004R0035 (V
O
2.1V)
(13)
Kemet, Poly-Tantalum
T520 (SMD)
10
330
25
2600
7,3
4,3
4,1
1
1
3
C
2
(8)
T520X337M010ASE025
T530 (SMD)
6.3
330
15
3800
7,3
4,3
4,1
1
1
2
B
2
(8)
T530X337M010ASE015
(10)
T530 (SMD)
4
680
5
7300
7,3
4,3
4,1
N/R
(9)
N/R
(11)
B
1
(8)
T530X687M004ASE005 (V
O
3.2V)
(10)
T530 (SMD)
2.5
1000
5
7300
7,3
4,3
4,1
N/R
(9)
N/R
(11)
B
1
(8)
T530X108M2R5ASE005 (V
O
2.0V)
(10)
Vishay-Sprague
597D, Tantalum (SMD)
10
330
35
2500
7,3
5,7
4,1
1
1
5
N/R
(12)
597D337X010E2T
94SP, OS-CON (Radial)
6.3
390
16
3810
8 X 10,5
1
1
2
C
2
(8)
94SP397X06R3EBP
94SVP OS-CON(SMD)
6.3
470
17
3960
8
12
1
1
2
C
1
(8)
94SVP477X06F12
Kemet, Ceramic X5R
6.3
100
2
3225
1
1
(14)
A
(8)
C1210C107M9PAC
(SMD)
6.3
47
2
1
2
(14)
A
(8)
C1210C476K9PAC
Murata, Ceramic X5R
6.3
100
2
3225
1
1
(14)
A
(8)
GRM32ER60J107M
(SMD)
6.3
47
1
2
(14)
A
(8)
GRM32ER60J476ME20L
16
22
1
5
(14)
A
(8)
GRM32ER61CE226KE20L
16
10
1
1
(14)
A
(8)
GRM32DR61C106K
TDK, Ceramic X5R
6.3
100
2
3225
1
1
(14)
A
(8)
C3225X5R0J107MT
(SMD)
6.3
47
1
1
(14)
A
(8)
C3225X5R0J476MT
16
10
1
1
(14)
A
(8)
C3225X5R1C106MT0
16
22
1
1
(14)
A
(8)
C3225X5R1C226MT
(8)
Required capacitors with TurboTrans. See the TurboTrans Application information for Capacitor Selection
Capacitor Types:
Type A = (100 < capacitance
ESR
1000)
Type B = (1,000 < capacitance
ESR
5,000)
Type C = (5,000 < capacitance
ESR
10,000)
(9)
N/R Not recommended. The voltage rating does not meet the minimum operating limits.
(10) The voltage rating of this capacitor only allows it to be used for output voltage that is equal to or less than 80% of the working voltage.
(11) N/R Not recommended. The ESR value of this capacitor is below the required minimum when not using TurboTrans.
(12) Aluminum Electrolytic capacitor not recommended for the TurboTrans due to higher ESR
capacitance products. Aluminum and higher
ESR capacitors can be used in conjunction with lower ESR capacitance.
(13) The voltage rating of this capacitor only allows it to be used for output voltage that is equal to or less than 50% of the working voltage.
(14) Any combination of ceramic capacitor values is limited as listed in the Electrical Characteristics table.
16
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TURBOTRANS
TurboTransTM Technology
TurboTransTM Selection
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
TurboTrans technology is a feature introduced in the T2 generation of the PTH/PTV family of power modules.
TurboTrans optimizes the transient response of the regulator with added external capacitance using a single
external resistor. Benefits of this technology include reduced output capacitance, minimized output voltage
deviation following a load transient, and enhanced stability when using ultra-low ESR output capacitors. The
amount of output capacitance required to meet a target output voltage deviation is reduced with TurboTrans
activated. Likewise, for a given amount of output capacitance, with TurboTrans engaged, the amplitude of the
voltage deviation following a load transient is reduced. Applications requiring tight transient voltage tolerances
and minimized capacitor footprint area benefits greatly from this technology.
Using TurboTrans requires connecting a resistor, R
TT
, between the +Sense pin (pin 5) and the TurboTrans pin
(pin 8). The value of the resistor directly corresponds to the amount of output capacitance required. All T2
products require a minimum value of output capacitance whether or not TurboTrans is used. For the
PTH04T230W, the minimum required capacitance is 200
F ceramic. When using TurboTrans, capacitors with a
capacitance
ESR product below 10,000
F
m
are required. (Multiply the capacitance (in
F) by the ESR (in
m
) to determine the capacitance
ESR product.) See the Capacitor Selection section of the datasheet for a
variety of capacitors that meet this criteria.
Figure 10
shows the amount of output capacitance required to meet a desired transient voltage deviation with
and without TurboTrans for several capacitor types; Type A (e.g. ceramic), Type B (e.g. polymer-tantalum), and
Type C (e.g. OS-CON). To calculate the proper value of R
TT
, first determine the required transient voltage
deviation limits and magnitude of the transient load step. Next, determine what type of output capacitors is used.
(If more than one type of output capacitor is used, select the capacitor type that makes up the majority of the
total output capacitance). Knowing this information, use the chart in
Figure 10
that corresponds to the capacitor
type selected. To use the chart, begin by dividing the maximum voltage deviation limit (in mV) by the magnitude
of the load step (in Amps). This gives a mV/A value. Find this value on the Y-axis of the appropriate chart. Read
across the graph to the 'With TurboTrans' plot. From this point, read down to the X-axis which lists the minimum
required capacitance, C
O
, to meet that transient voltage deviation. The required R
TT
resistor value can then be
calculated using the equation or selected from the TurboTrans table. The TurboTrans tables include both the
required output capacitance and the corresponding R
TT
values to meet several values of transient voltage
deviation for 25% (1.5 A), 50% (3 A), and 75% (4.5 A) output load steps.
The chart can also be used to determine the achievable transient voltage deviation for a given amount of output
capacitance. Selecting the amount of output capacitance along the X-axis, reading up to the 'With TurboTrans'
curve, and then over to the Y-axis, gives the transient voltage deviation limit for that value of output capacitance.
The required R
TT
resistor value can be calculated using the equation or selected from the TurboTrans table.
As an example, consider a 5-V application requiring a 45 mV deviation during a 3-A, 50% load transient. A
majority of 330
F, 10 m
ouput capacitors are used. Use the Type B capacitor chart,
Figure 11
. Dividing 45 mV
by 3 A gives 15 mV/A transient voltage deviation per amp of transient load step. Select 15 mV/A on the Y-axis
and read across to the 'With TurboTrans' plot. Following this point down to the X-axis gives us a minimum
required output capacitance of approximately 820
F. The required R
TT
resistor value for 820
F can then be
calculated or selected from
Table 5
. The required R
TT
resistor is approximately 6.19 k
.
To see the benefit of TurboTrans, follow the 15 mV/A marking across to the 'Without TurboTrans' plot. Following
that point down shows that you would need a minimum of 2700
F of output capacitance to meet the same
transient deviation limit. This is the benefit of TurboTrans. A typical TurboTrans schematic is shown in
Figure 16
.
17
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C - Capacitance -
F
T
ransient - mV/A
40
30
20
4
5000
4000
3000
1000
900
300
200
500
400
700
600
800
2000
10
6
5
8
7
9
PTH04T231 Type A
Ceramic Capacitors
Without TurboTrans
With TurboTrans
C - Capacitance -
F
T
ransient - mV/A
40
30
20
4
5000
4000
3000
1000
900
300
200
500
400
700
600
800
2000
10
6
5
8
7
9
PTH04T231 Type A
Ceramic Capacitors
Without TurboTrans
With TurboTrans
R
TT
+
40
1
*
C
O
1500
C
O
300
*
1
k
W
(2)
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
PTH04T231W - Type A Ceramic Capacitors
5-V Input
3.3-V Input
Figure 10. Capacitor Type A, 100 < C(
F) x ESR(m
)
Figure 11. Capacitor Type A, 100 < C(
F) x ESR(m
)
1000
1000
(e.g. Ceramic)
(e.g. Ceramic)
Table 4. Type A TurboTrans C
O
Values and Required R
TT
Selection Table
Transient Voltage Deviation (mV)
5-V Input
3.3-V input
C
O
R
TT
C
O
R
TT
25% load step
50% load step
75% load step
Minimum
Required
Minimum
Required
(1.5 A)
(3 A)
(4.5 A)
Required Output
TurboTrans
Required Output
TurboTrans
Capacitance (
F)
Resistor (k
)
Capacitance (
F)
Resistor (k
)
40
80
120
300
open
300
open
35
70
105
320
549
300
open
30
60
90
400
93.1
350
226
25
50
75
510
37.4
450
59.0
20
40
60
700
15.8
610
22.6
15
30
45
1050
4.75
920
7.50
10
20
30
3300
short
2250
short
R
TT
Resistor Selection
The TurboTrans resistor value, R
TT
can be determined from the TurboTrans programming equation:
Where C
O
is the total output capacitance in
F. C
O
values greater than or equal to 1500
F require R
TT
to
be a short, 0
.
To ensure stability, a minimum amount of output capacitance is required for a given R
TT
resistor value. The
value of R
TT
must be calculated using the minimum required output capacitance determined from the
capacitor transient response charts above.
18
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40
30
20
4
5000
4000
3000
1000
900
300
200
500
400
700
600
800
2000
10
With TurboTrans
Without TurboTrans
6
5
8
7
9
C - Capacitance -
F
T
ransient - mV/A
C - Capacitance -
F
T
ransient - mV/A
Without TurboTrans
With TurboTrans
40
30
20
4
5000
4000
3000
1000
900
300
200
500
400
700
600
800
2000
10
6
5
8
7
9
R
TT
+
40
1
*
C
O
1250
C
O
250
*
1
k
W
(3)
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
PTH04T230W Type B Capacitors
5-V Input
3.3-V Input
Figure 12. Capacitor Type B, 1000 < C(
F) x ESR(m
)
Figure 13. Capacitor Type B, 1000 < C(
F) x ESR(m
)
5000
5000
(e.g. Polymer-Tantalum)
(e.g. Polymer-Tantalum)
Table 5. Type B TurboTrans C
O
Values and Required R
TT
Selection Table
Transient Voltage Deviation (mV)
5-V Input
3.3-V Input
C
O
R
TT
C
O
R
TT
25% load step
50% load step
75% load step
Minimum
Required
Minimum
Required
(1.5 A)
(3 A)
(4.5 A)
Required Output
TurboTrans
Required Output
TurboTrans
Capacitance (
F)
Resistor (k
)
Capacitance (
F)
Resistor (k
)
60
120
180
250
open
250
open
50
100
150
300
165
300
165
40
80
120
400
46.4
400
46.4
30
60
90
570
16.9
570
16.9
25
50
75
710
9.31
720
9.09
20
40
60
940
3.57
960
3.24
15
30
45
1520
short
1500
short
12
24
36
3200
short
3100
short
R
TT
Resistor Selection
The TurboTrans resistor value, R
TT
can be determined from the TurboTrans programming equation:
Where C
O
is the total output capacitance in
F. C
O
values greater than or equal to 1250
F require R
TT
to
be a short, 0
.
To ensure stability, a minimum amount of output capacitance is required for a given R
TT
resistor value. The
value of R
TT
must be calculated using the minimum required output capacitance determined from the
capacitor transient response charts above.
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C - Capacitance -
F
T
ransient - mV/A
Without TurboTrans
With TurboTrans
40
30
20
4
5000
4000
3000
1000
900
300
200
500
400
700
600
800
2000
10
6
5
8
7
9
C - Capacitance -
F
T
ransient - mV/A
Without TurboTrans
With TurboTrans
40
30
20
4
5000
4000
3000
1000
900
300
200
500
400
700
600
800
2000
10
6
5
8
7
9
R
TT
+
40
1
*
C
O
1250
C
O
250
*
1
k
W
(4)
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
PTH04T230W Type C Capacitors
5-V Input
3.3-V Input
Figure 14. Capacitor Type C, 5000 < C(
F) x ESR(m
)
Figure 15. Capacitor Type C, 5000 < C(
F) x ESR(m
)
10,000
10,000
(e.g. OS-CON)
(e.g. OS-CON)
Table 6. Type C TurboTrans C
O
Values and Required R
TT
Selection Table
Transient Voltage Deviation (mV)
5-V Input
3.3 V Input
C
O
R
TT
C
O
R
TT
Minimum
Required
Minimum
Required
25% load step
50% load step
75% load step
Required Output
TurboTrans
Required Output
TurboTrans
(1.5 A)
(3 A)
(4.5 A)
Capacitance
Resistor (k
)
Capacitance (
F)
Resistor (k
)
(
F)
50
100
150
270
487
250
open
40
80
120
360
66.5
350
76.8
35
70
105
430
36.5
420
39.2
30
60
90
520
21.5
520
21.5
25
50
75
660
11.5
670
11.0
20
40
60
890
4.53
920
3.83
15
30
45
1420
short
1630
short
12
20
30
3050
short
3700
short
R
TT
Resistor Selection
The TurboTrans resistor value, R
TT
can be determined from the TurboTrans programming equation:
Where C
O
is the total output capacitance in
F. C
O
values greater than or equal to 1250
F require R
TT
to
be a short, 0
.
To ensure stability, a minimum amount of output capacitance is required for a given R
TT
resistor value. The
value of R
TT
must be calculated using the minimum required output capacitance determined from the
capacitor transient response charts above.
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UDG-06047
PTH04T230W
7
AutoTrack
VoAdj
TT
3
GND
GND
+Sense
L
O
A
D
-Sense
GND
+
INH/UVLO
+Sense
SYNC
R
TT
0 k
(Note A)
R
SET
1%
0.05 W
C
O1
200
F
Ceramic
C
I
330
F
(Required)
C
O2
1320
F
Type B
V
I
V
O
V
O
V
I
TurboTrans
E
T - Time - 200
s/div
PTH04T230
C
O
= 1520
F
Without TurboTrans
TM
50 mV/div
With TurboTrans
TM
50 mV/div
50% Load Step
2.5 A/
s
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
A.
The value of R
TT
must be calculated using the total value of output capacitance.
Figure 16. Typical TurboTransTM Schematic
Figure 17. Typical TurboTrans Waveforms
21
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UNDERVOLTAGE LOCKOUT (UVLO)
R
UVLO
+
68.54
*
V
THD
V
THD
*
2.07
k
W
(5)
GND
2
3
+
GND
Inhibit/
UVLO
10
V
I
V
I
C
I
UDG-06059
PTH04T230/231W
R
UVLO
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
The PTH04T230/231W power modules incorporate an input undervoltage lockout (UVLO). The UVLO feature
prevents the operation of the module until there is sufficient input voltage to produce a valid output voltage. This
enables the module to provide a clean, monotonic power-up for the load circuit, and also limits the magnitude of
current drawn from the regulator's input source during the power-up sequence.
The UVLO characteristic is defined by the ON threshold (V
THD
) voltage. Below the ON threshold, the Inhibit
control is overridden, and the module does not produce an output. The hysteresis voltage, which is the
difference between the ON and OFF threshold voltages, is set at 500 mV. The hysteresis prevents start-up
oscillations, which can occur if the input voltage droops slightly when the module begins drawing current from
the input source.
The UVLO feature of the PTH04T230/231W module allows for limited adjustment of the ON threshold voltage.
The adjustment is made via the Inhbit/UVLO Prog control pin (pin 10) using a single resistor (see figure below).
When pin 10 is left open circuit, the ON threshold voltage is internally set to its default value, which is 1.95 volts.
The ON threshold might need to be raised if the module is powered from a tightly regulated 5-V bus. Adjusting
the threshold prevents the module from operating if the input bus fails to completely rise to its specified
regulation voltage.
Equation 5
determines the value of R
UVLO
required to adjust V
THD
to a new value. The default value is 1.95 V,
and it may only be adjusted to a higher value.
Table 7
lists the standard resistor values for R
UVLO
for different values of the ON-threshold (V
THD
) voltage.
Table 7. Standard R
UVLO
Values for Various V
THD
Values
V
THD
(V)
2.5
3.0
3.5
4.0
4.5
R
UVLO
(k
)
154
71.5
53.6
33.2
26.7
Figure 18. Undervoltage Lockout
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Soft-Start Power Up
UDG-06044
V
I
V
I
Track
GND
2
9
3
+
GND
C
I
PTH04T230/231W
V
I
(2 V/div)
V
O
(1 V/div)
I
I
(2 A/div)
T - Time - 4 ms/div
Remote Sense
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
The Auto-Track feature allows the power-up of multiple PTH/PTV modules to be directly controlled from the
Track pin. However in a stand-alone configuration, or when the Auto-Track feature is not being used, the Track
pin should be directly connected to the input voltage, V
I
(see
Figure 19
).
Figure 19. Defeating the Auto-Track Function
Figure 20. Power-Up Waveform
When the Track pin is connected to the input voltage the Auto-Track function is permanently disengaged. This
allows the module to power up entirely under the control of its internal soft-start circuitry. When power up is
under soft-start control, the output voltage rises to the set-point at a quicker and more linear rate. From the
moment a valid input voltage is applied, the soft-start control introduces a short time delay (typically
2 ms10 ms) before allowing the output voltage to rise. The output then progressively rises to the module's
setpoint voltage.
Figure 20
shows the soft-start power-up characteristic of the PTH04T230/231W operating from a 5-V input bus
and configured for a 1.8-V output. The waveforms were measured with a 6-A constant current load and the
Auto-Track feature disabled. The initial rise in input current when the input voltage first starts to rise is the
charge current drawn by the input capacitors. Power-up is complete within 20 ms.
Differential remote sense improves the load regulation performance of the module by allowing it to compensate
for any IR voltage drop between its output and the load in either the positive or return path. An IR drop is caused
by the output current flowing through the small amount of pin and trace resistance. Connecting the +Sense (pin
5) and Sense (pin 6) pins to the respective positive and ground reference of the load terminals improves the
load regulation of the output voltage at the connection points.
With the sense pins connected at the load, the difference between the voltage measured directly between the
V
O
and GND pins, and that measured at the Sense pins, is the amount of IR drop being compensated by the
regulator. This should be limited to a maximum of 300 mV.
If the remote sense feature is not used at the load, connect the +Sense pin to V
O
(pin 4) and connect the
Sense pin to the module GND (pin 3).
The remote sense feature is not designed to compensate for the forward drop of nonlinear or frequency
dependent components that may be placed in series with the converter output. Examples include OR-ing
diodes, filter inductors, ferrite beads, and fuses. When these components are enclosed by the remote sense
connection they are effectively placed inside the regulation control loop, which can adversely affect the
stability of the regulator.
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Output On/Off Inhibit
GND
PTH04T230/231W
2
3
+
GND
Inhibit/
UVLO
1 = Inhibit
Q1
BSS138
10
V
I
V
I
C
I
UDG-06045
T - Time - 4 ms/div
V
O
(1 V/div)
I
I
(2 A/div)
V
INH
(2 V/div)
Overcurrent Protection
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
For applications requiring output voltage on/off control, the PTH04T230/231W incorporates an output Inhibit
control pin. The inhibit feature can be used wherever there is a requirement for the output voltage from the
regulator to be turned off.
The power modules function normally when the Inhibit pin is left open-circuit, providing a regulated output
whenever a valid source voltage is connected to V
I
with respect to GND.
Figure 21
shows the typical application of the inhibit function. Note the discrete transistor (Q1). The Inhibit input
has its own internal pull-up. An external pull-up should never be connected to the inhibit pin. The input is not
compatible with TTL logic devices. An open-collector (or open-drain) discrete transistor is recommended for
control.
Figure 21. On/Off Inhibit Control Circuit
Figure 22. Power-Up Response from Inhibit Control
Turning Q1 on applies a low voltage to the Inhibit control pin and disables the output of the module. If Q1 is then
turned off, the module executes a soft-start power-up sequence. A regulated output voltage is produced within
40 ms.
Figure 22
shows the typical rise in both the output voltage and input current, following the turn-off of Q1.
The turn off of Q1 corresponds to the rise in the waveform, V
INH
. The waveforms were measured with a 3-A
constant current load.
For protection against load faults, all modules incorporate output overcurrent protection. Applying a load that
exceeds the regulator's overcurrent threshold causes the regulated output to shut down. Following shutdown, a
module periodically attempts to recover by initiating a soft-start power-up. This is described as a hiccup mode of
operation, whereby the module continues in a cycle of successive shutdown and power up until the load fault is
removed. During this period, the average current flowing into the fault is significantly reduced. Once the fault is
removed, the module automatically recovers and returns to normal operation.
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Overtemperature Protection (OTP)
Smart Sync
PTH04T240W
Vi
Track
GND
VoAdj
Vo
TT
+Sense
-Sense
Inhibit/
UVLO
GND
D
PRE
PTH04T230W
Vi
GND
VoAdj
Vo
TT
+Sense
-Sense
+
Inhibit/
UVLO
Sync
+
+
Q
CLK
SN74LVC2G74
+
SYNC
R
SET1
f
CLK
= 2 x f
MODULE
V
O1
0
180
V
CC
CLR
Q
V
O2
C
O1
C
O2
UDG-06054
C
I1
C
I2
R
SET2
Track
V
I
=5 V
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
A thermal shutdown mechanism protects the module's internal circuitry against excessively high temperatures. A
rise in the internal temperature may be the result of a drop in airflow, or a high ambient temperature. If the
internal temperature exceeds the OTP threshold, the module's Inhibit control is internally pulled low. This turns
the output off. The output voltage drops as the external output capacitors are discharged by the load circuit. The
recovery is automatic, and begins with a soft-start power up. It occurs when the sensed temperature decreases
by about 10
C below the trip point.
The overtemperature protection is a last resort mechanism to prevent thermal stress to the regulator.
Operation at or close to the thermal shutdown temperature is not recommended and reduces the long-term
reliability of the module. Always operate the regulator within the specified safe operating area (SOA) limits
for the worst-case conditions of ambient temperature and airflow.
Smart Sync is a feature that allows multiple power modules to be synchronized to a common frequency. Driving
the Smart Sync pins with an external oscillator set to the desired frequency, synchronizes all connected modules
to the selected frequency. The synchronization frequency can be higher or lower than the nominal switching
frequency of the modules within the range of 240 kHz to 400 kHz (see Electrical Specifications table for
frequency limits). Synchronizing modules powered from the same bus eliminates beat frequencies reflected back
to the input supply, and also reduces EMI filtering requirements. These are the benefits of Smart Sync. Power
modules can also be synchronized out of phase to minimize source current loading and minimize input
capacitance requirements.
Figure 23
shows a standard circuit with two modules syncronized 180
out of phase
using a D flip-flop.
Figure 23. Typical SmartSync Circuit
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Auto-TrackTM Function
How Auto-TrackTM Works
Typical Application
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
The Auto-Track function is unique to the PTH/PTV family, and is available with all POLA products. Auto-Track
was designed to simplify the amount of circuitry required to make the output voltage from each module power up
and power down in sequence. The sequencing of two or more supply voltages during power up is a common
requirement for complex mixed-signal applications that use dual-voltage VLSI ICs such as the TMS320TM DSP
family, microprocessors, and ASICs.
Auto-Track works by forcing the module output voltage to follow a voltage presented at the Track control pin
(1)
.
This control range is limited to between 0 V and the module set-point voltage. Once the track-pin voltage is
raised above the set-point voltage, the module output remains at its set-point
(2)
. As an example, if the Track pin
of a 2.5-V regulator is at 1 V, the regulated output is 1 V. If the voltage at the Track pin rises to 3 V, the
regulated output does not go higher than 2.5 V.
When under Auto-Track control, the regulated output from the module follows the voltage at its Track pin on a
volt-for-volt basis. By connecting the Track pin of a number of these modules together, the output voltages follow
a common signal during power up and power down. The control signal can be an externally generated master
ramp waveform, or the output voltage from another power supply circuit
(3)
. For convenience, the Track input
incorporates an internal RC-charge circuit. This operates off the module input voltage to produce a suitable
rising waveform at power up.
The basic implementation of Auto-Track allows for simultaneous voltage sequencing of a number of Auto-Track
compliant modules. Connecting the Track inputs of two or more modules forces their track input to follow the
same collective RC-ramp waveform, and allows their power-up sequence to be coordinated from a common
Track control signal. This can be an open-collector (or open-drain) device, such as a power-up reset voltage
supervisor IC. See U3 in
Figure 24
.
To coordinate a power-up sequence, the Track control must first be pulled to ground potential. This should be
done at or before input power is applied to the modules. The ground signal should be maintained for at least
20 ms after input power has been applied. This brief period gives the modules time to complete their internal
soft-start initialization
(4)
, enabling them to produce an output voltage. A low-cost supply voltage supervisor IC,
that includes a built-in time delay, is an ideal component for automatically controlling the Track inputs at power
up.
Figure 24
shows how a TPS3808 supply voltage supervisor IC (U3) can be used to coordinate the sequenced
power up of 5-V PTH modules. The output of the TPS3808 supervisor becomes active above an input voltage of
0.8 V, enabling it to assert a ground signal to the common track control well before the input voltage has
reached the module's undervoltage lockout threshold. The ground signal is maintained until approximately 27 ms
after the input voltage has risen above U3's voltage threshold, which is 4.65 V. The 27-ms time period is
controlled by the capacitor C3. The value of 4700 pF provides sufficient time delay for the modules to complete
their internal soft-start initialization. The output voltage of each module remains at zero until the track control
voltage is allowed to rise. When U3 removes the ground signal, the track control voltage automatically rises.
This causes the output voltage of each module to rise simultaneously with the other modules, until each reaches
its respective set-point voltage.
Figure 25
shows the output voltage waveforms after input voltage is applied to the circuit. The waveforms, V
O
1
and V
O
2, represent the output voltages from the two power modules, U1 (3.3 V) and U2 (1.8 V), respectively.
V
TRK
, V
O
1, and V
O
2 are shown rising together to produce the desired simultaneous power-up characteristic.
The same circuit also provides a power-down sequence. When the input voltage falls below U3's voltage
threshold, the ground signal is re-applied to the common track control. This pulls the track inputs to zero volts,
forcing the output of each module to follow, as shown in
Figure 26
. Power down is normally complete before the
input voltage has fallen below the modules' undervoltage lockout. This is an important constraint. Once the
modules recognize that an input voltage is no longer present, their outputs can no longer follow the voltage
applied at their track input. During a power-down sequence, the fall in the output voltage from the modules is
limited by the Auto-Track slew rate capability.
26
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Notes on Use of Auto-TrackTM
U2
PTH04T230W
Vi
Auto Track
GND
VoAdj
Vo
TurboTrans
+Sense
-Sense
Inhibit/
UVLO
U3
TPS3808G50
6
GND
2
4
3
MR
CT
SENSE
5
1
U1
PTH05T210W
Vi
Auto Track
GND
VoAdj
Vo
TurboTrans
+Sense
-Sense
+
Inhibit/
UVLO
SmartSync
+
R
TT
V
O1
= 3.3 V
C
O1
V
O2
= 1.8 V
C
O2
R
TT
R
SET2
4.75 k
R
SET1
1.62 k
C
I2
C
I1
RESET
V
I
= 5 V
C
4
0.1
F
C
3
4700
F
UDG-06042
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
1. The Track pin voltage must be allowed to rise above the module set-point voltage before the module
regulates at its adjusted set-point voltage.
2. The Auto-Track function tracks almost any voltage ramp during power up, and is compatible with ramp
speeds of up to 1 V/ms.
3. The absolute maximum voltage that may be applied to the Track pin is the input voltage V
I
.
4. The module cannot follow a voltage at its track control input until it has completed its soft-start initialization.
This takes about 20 ms from the time that a valid voltage has been applied to its input. During this period, it
is recommended that the Track pin be held at ground potential.
5. The Auto-Track function is disabled by connecting the Track pin to the input voltage (V
I
). When Auto-Track
is disabled, the output voltage rises at a quicker and more linear rate after input power has been applied.
Figure 24. Sequenced Power Up and Power Down Using Auto-Track
27
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T - Time - 20 ms/div
V
TRK
(1 V/div)
V
01
(1 V/div)
V
02
(1 V/div)
T - Time - 200
s/div
V
TRK
(1 V/div)
V
01
(1 V/div)
V
02
(1 V/div)
Prebias Startup Capability
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
Figure 25. Simultaneous Power Up With Auto-Track
Figure 26. Simultaneous Power Down With Auto-Track
Control
Control
A prebias startup condition occurs as a result of an external voltage being present at the output of a power
module prior to its output becoming active. This often occurs in complex digital systems when current from
another power source is backfed through a dual-supply logic component, such as an FPGA or ASIC. Another
path might be via clamp diodes as part of a dual-supply power-up sequencing arrangement. A prebias can
cause problems with power modules that incorporate synchronous rectifiers. This is because under most
operating conditions, these types of modules can sink as well as source output current.
The PTH family of power modules incorporate synchronous rectifiers, but does not sink current during startup
(1)
,
or whenever the Inhibit pin is held low. However, to ensure satisfactory operation of this function, certain
conditions must be maintained
(2)
.
Figure 27
shows an application demonstrating the prebias startup capability.
The startup waveforms are shown in
Figure 28
. Note that the output current (I
O
) is negligible until the output
voltage rises above the voltage backfed through the intrinsic diodes.
The prebias start-up feature is not compatible with Auto-Track. When the module is under Auto-Track control, it
sinks current if the output voltage is below that of a back-feeding source. To ensure a pre-bias hold-off one of
two approaches must be followed when input power is applied to the module. The Auto-Track function must
either be disabled
(3)
, or the module's output held off (for at least 50 ms) using the Inhibit pin. Either approach
ensures that the Track pin voltage is above the set-point voltage at start up.
1. Startup includes the short delay (approximately 10 ms) prior to the output voltage rising, followed by the rise
of the output voltage under the module's internal soft-start control. Startup is complete when the output
voltage has risen to either the set-point voltage or the voltage at the Track pin, whichever is lowest.
2. To ensure that the regulator does not sink current when power is first applied (even with a ground signal
applied to the Inhibit control pin), the input voltage must always be greater than the output voltage
throughout the power-up and power-down sequence.
3. The Auto-Track function can be disabled at power up by immediately applying a voltage to the module's
Track pin that is greater than its set-point voltage. This can be easily accomplished by connecting the Track
pin to V
I
.
28
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GND
PTH04T230W
+
VCORE
VCCIO
ASIC
Track
Inhibit
-Sense
+Sense
3.3 V
V
O
Adj
R
SET
2.37 k
C
O
200
F
V
O
= 2.5 V
I
O
V
I
= 5 V
C
I
330
F
UDG-06055
V
I
V
O
t - Time = 4 ms/div
V
(1 V/div)
O
I
(2 A/div)
O
V
(1 V/div)
IN
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
Figure 27. Application Circuit Demonstrating Prebias Startup
Figure 28. Prebias Startup Waveforms
29
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TAPE AND REEL & TRAY DRAWINGS
PTH04T230W, PTH04T231W
SLTS271A SEPTEMBER 2006 REVISED OCTOBER 2006
30
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PACKAGING INFORMATION
Orderable Device
Status
(1)
Package
Type
Package
Drawing
Pins Package
Qty
Eco Plan
(2)
Lead/Ball Finish
MSL Peak Temp
(3)
PTH04T230WAD
ACTIVE
DIP MOD
ULE
ECL
10
36
Pb-Free
(RoHS)
Call TI
N / A for Pkg Type
PTH04T230WAS
ACTIVE
DIP MOD
ULE
ECM
10
36
TBD
Call TI
Level-1-235C-UNLIM
PTH04T230WAST
ACTIVE
DIP MOD
ULE
ECM
10
250
TBD
Call TI
Level-1-235C-UNLIM
PTH04T230WAZ
ACTIVE
DIP MOD
ULE
BCM
10
36
Pb-Free
(RoHS)
Call TI
Level-3-260C-168 HR
PTH04T230WAZT
ACTIVE
DIP MOD
ULE
BCM
10
250
Pb-Free
(RoHS)
Call TI
Level-3-260C-168 HR
PTH04T231WAD
ACTIVE
DIP MOD
ULE
ECL
10
36
Pb-Free
(RoHS)
Call TI
N / A for Pkg Type
PTH04T231WAS
ACTIVE
DIP MOD
ULE
ECM
10
36
TBD
Call TI
Level-1-235C-UNLIM
PTH04T231WAST
ACTIVE
DIP MOD
ULE
ECM
10
250
TBD
Call TI
Level-1-235C-UNLIM
PTH04T231WAZ
ACTIVE
DIP MOD
ULE
BCM
10
36
Pb-Free
(RoHS)
Call TI
Level-3-260C-168 HR
PTH04T231WAZT
ACTIVE
DIP MOD
ULE
BCM
10
250
Pb-Free
(RoHS)
Call TI
Level-3-260C-168 HR
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in
a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check
http://www.ti.com/productcontent
for the latest availability information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements
for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered
at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and
package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS
compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame
retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material)
(3)
MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder
temperature.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is
provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the
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reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on
incoming materials and chemicals. TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited
information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI
to Customer on an annual basis.
PACKAGE OPTION ADDENDUM
www.ti.com
3-Nov-2006
Addendum-Page 1
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